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FEATURES

LTC2486 16-Bit 2-/4-Channel ADC with PGA and Easy Drive Input Current Cancellation DESCRIPTION
The LTC(R)2486 is a 4-channel (2-channel differential), 16-bit, No Latency TM ADC with Easy DriveTM technology. The patented sampling scheme eliminates dynamic input current errors and the shortcomings of on-chip buffering through automatic cancellation of differential input current. This allows large external source impedances and rail-torail input signals to be directly digitized while maintaining exceptional DC accuracy. The LTC2486 includes programmable gain, a high accuracy temperature sensor, and an integrated oscillator. This device can be configured to measure an external signal (from combinations of 4 analog input channels operating in single ended or differential modes) or its internal temperature sensor. It can be programmed to reject line frequencies of 50Hz, 60Hz, or simultaneous 50Hz/60Hz, provide a programmable gain from 1 to 256 in 8 steps, and configured to double its output rate. The integrated temperature sensor offers 1/2C resolution and 2C absolute accuracy. The LTC2486 allows a wide common mode input range (0V to VCC), independent of the reference voltage. Any combination of single-ended or differential inputs can be selected and the first conversion after a new channel selection is valid.
, LT, LTC and LTM are registered trademarks of Linear Technology Corporation. No Latency and Easy Drive are trademarks of Linear Technology Corporation. All other trademarks are the property of their respective owners.
Up to 2 Differential or 4 Single-Ended Inputs Easy Drive Technology Enables Rail-to-Rail Inputs with Zero Differential Input Current Directly Digitizes High Impedance Sensors with Full Accuracy 600nV RMS Noise Programmable Gain from 1 to 256 Integrated High Accuracy Temperature Sensor GND to VCC Input/Reference Common Mode Range Programmable 50Hz, 60Hz, or Simultaneous 50Hz/60Hz Rejection Mode 2ppm INL, No Missing Codes 1ppm Offset and 15ppm Full-Scale Error 2x Speed Mode/Reduced Power Mode (15Hz Using Internal Oscillator and 80A at 7.5Hz Output) No Latency: Digital Filter Settles in a Single Cycle, Even After a New Channel is Selected Single Supply 2.7V to 5.5V Operation (0.8mW) Internal Oscillator Tiny 4mm x 3mm DFN Package
APPLICATIONS

Direct Sensor Digitizer Direct Temperature Measurement Instrumentation Industrial Process Control
TYPICAL APPLICATION
Data Acquisition System with Temperature Compensation
2.7V TO 5.5V 0.1F 10F
ABSOLUTE ERROR (C) 5 4
Absolute Temperature Error
CH0 CH1 REF +
VCC
3 2 1 0 -1 -2 -3 -4
4-CHANNEL MUX CH2 CH3 COM TEMPERATURE SENSOR
IN
+
16-BIT ADC WITH EASY-DRIVE IN- REF -
SDI SCK SDO CS
4-WIRE SPI INTERFACE
FO OSC
2486 TA01a
-5 -55
-30
-5 20 45 70 TEMPERATURE (C)
95
120
2486 TA01b
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LTC2486 ABSOLUTE MAXIMUM RATINGS
(Notes 1, 2)
PACKAGE/ORDER INFORMATION
FO SDI SCK CS SDO GND COM 1 2 3 4 5 6 7 15 14 REF- 13 REF+ 12 VCC 11 CH3 10 CH2 9 CH1 8 CH0
Supply Voltage (VCC) ................................... -0.3V to 6V Analog Input Voltage (CH0 to CH3, COM) ..................-0.3V to (VCC + 0.3V) REF+, REF- ................................-0.3V to (VCC + 0.3V) Digital Input Voltage......................-0.3V to (VCC + 0.3V) Digital Output Voltage ...................-0.3V to (VCC + 0.3V) Operating Temperature Range LTC2486C ................................................ 0C to 70C LTC2486I ............................................. -40C to 85C Storage Temperature Range................... -65C to 150C
DE PACKAGE 14-LEAD (4mm x 3mm) PLASTIC DFN TJMAX = 125C, JA = 37C/W EXPOSED PAD (PIN 15) IS GND, MUST BE SOLDERED TO PCB
ORDER PART NUMBER LTC2486CDE LTC2486IDE
DE PART MARKING* 2486 2486
Order Options Tape and Reel: Add #TR Lead Free: Add #PBF Lead Free Tape and Reel: Add #TRPBF Lead Free Part Marking: http://www.linear.com/leadfree/ Consult LTC Marketing for parts specified with wider operating temperature ranges. *The temperature grade is identified by a label on the shipping container.
ELECTRICAL CHARACTERISTICS (NORMAL SPEED)
PARAMETER Resolution (No Missing Codes) Integral Nonlinearity Offset Error Offset Error Drift Positive Full-Scale Error Positive Full-Scale Error Drift Negative Full-Scale Error Negative Full-Scale Error Drift Total Unadjusted Error CONDITIONS 0.1V VREF VCC, -FS VIN +FS (Note 5) 5V VCC 5.5V, VREF = 5V, VIN(CM) = 2.5V (Note 6) 2.7V VCC 5.5V, VREF = 2.5V, VIN(CM) = 1.25V (Note 6) 2.5V VREF VCC, GND IN+ = IN- VCC (Note 14) 2.5V VREF VCC, GND IN+ = IN- VCC 2.5V VREF VCC, IN+ = 0.75VREF, IN- = 0.25VREF 2.5V VREF VCC, IN+ = 0.75VREF, IN- = 0.25VREF 2.5V VREF VCC, IN+ = 0.25VREF, IN- = 0.75VREF 2.5V VREF VCC, IN+ = 0.25VREF, IN- = 0.75VREF 5V VCC 5.5V, VREF = 2.5V, VIN(CM) = 1.25V 5V VCC 5.5V, VREF = 5V, VIN(CM) = 2.5V 2.7V VCC 5.5V, VREF = 2.5V, VIN(CM) = 1.25V 5.5V < VCC < 2.7V, 2.5V VREF VCC, GND IN+ = IN- VCC (Note 13) TA = 27C (Note 14)

The denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25C. (Notes 3, 4)
MIN 16 2 1 0.5 10 32 0.1
TYP
MAX 20 5
UNITS Bits ppm of VREF ppm of VREF V nV/C ppm of VREF ppm of VREF/C ppm of VREF ppm of VREF/C ppm of VREF ppm of VREF ppm of VREF VRMS
32 0.1 15 15 15 0.6 27.8 1 28.0 93.5 256 28.2
Output Noise Internal PTAT Signal Internal PTAT Temperature Coefficient Programmable Gain
mV V/C
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LTC2486 ELECTRICAL CHARACTERISTICS (2X SPEED)
PARAMETER Resolution (No Missing Codes) Integral Nonlinearity Offset Error Offset Error Drift Positive Full-Scale Error Positive Full-Scale Error Drift Negative Full-Scale Error Negative Full-Scale Error Drift Output Noise Programmable Gain CONDITIONS 0.1V VREF VCC, -FS VIN +FS (Note 5) 5V VCC 5.5V, VREF = 5V, VIN(CM) = 2.5V (Note 6) 2.7V VCC 5.5V, VREF = 2.5V, VIN(CM) = 1.25V (Note 6) 2.5V VREF VCC, GND IN+ = IN- VCC (Note 14) 2.5V VREF VCC, GND IN+ = IN- VCC 2.5V VREF VCC, IN+ = 0.75VREF, IN- = 0.25VREF 2.5V VREF VCC, IN+ = 0.75VREF, IN- = 0.25VREF 2.5V VREF VCC, IN+ = 0.25VREF, IN- = 0.75VREF 2.5V VREF VCC, IN+ = 0.25VREF, IN- = 0.75VREF 2.7V VCC 5.5V, 2.5V VREF VCC, GND IN+ = IN- VCC

The denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25C. (Notes 3, 4)
MIN 16 2 1 0.2 100 32 0.1
TYP
MAX 20 2
UNITS Bits ppm of VREF ppm of VREF mV nV/C ppm of VREF ppm of VREF/C ppm of VREF ppm of VREF/C VRMS
32 0.1 0.85
1
128
CONVERTER CHARACTERISTICS
PARAMETER Input Common Mode Rejection DC Input Common Mode Rejection 50Hz 2% Input Common Mode Rejection 60Hz 2% Input Normal Mode Rejection 50Hz 2% Input Normal Mode Rejection 60Hz 2% Input Normal Mode Rejection 50Hz/60Hz 2% Reference Common Mode Rejection DC Power Supply Rejection DC Power Supply Rejection, 50Hz 2% Power Supply Rejection, 60Hz 2% CONDITIONS
The denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25C. (Note 3)
MIN

TYP
MAX
UNITS dB dB dB
2.5V VREF VCC, GND IN+ = IN- VCC (Note 5) 2.5V VREF VCC, GND IN+ = IN- VCC (Note 5) 2.5V VREF VCC, GND IN+ = IN- VCC (Note 5) 2.5V VREF VCC, GND IN+ = IN- VCC (Notes 5, 7) 2.5V VREF VCC, GND IN+ = IN- VCC (Notes 5, 8) 2.5V VREF VCC, GND IN+ = IN- VCC (Notes 5, 9) 2.5V VREF VCC, GND IN+ = IN- VCC (Note 5) VREF = 2.5V, IN+ = IN- = GND VREF = 2.5V, IN+ = IN- = GND (Notes 7, 9) VREF = 2.5V, IN+ = IN- = GND (Notes 8, 9)
140 140 140 110 110 87 120 140 120 120 120 120 120
dB dB dB dB dB dB dB
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LTC2486 ANALOG INPUT AND REFERENCE
SYMBOL IN+ IN- VIN FS LSB REF+ REF- VREF CS(IN+) CS(IN-) CS(VREF) IDC_LEAK(IN+) IDC_LEAK(IN-) IDC_LEAK(REF+) IDC_LEAK(REF-) tOPEN QIRR PARAMETER Absolute/Common Mode IN+ Voltage (IN+ Corresponds to the Selected Positive Input Channel) Absolute/Common Mode IN- Voltage (IN- Corresponds to the Selected Negative Input Channel) Input Differential Voltage Range (IN+ - IN-) Full Scale of the Differential Input (IN+ - IN-) Least Significant Bit of the Output Code Absolute/Common Mode REF+ Voltage Absolute/Common Mode REF- Voltage Reference Voltage Range (REF+ - REF-) IN+ Sampling Capacitance IN- Sampling Capacitance VREF Sampling Capacitance IN+ DC Leakage Current IN- DC Leakage Current REF+ DC Leakage Current REF- DC Leakage Current MUX Break-Before-Make MUX Off Isolation VIN = 2VP-P DC to 1.8MHz Sleep Mode, IN+ = GND Sleep Mode, IN- = GND Sleep Mode, REF+ = VCC Sleep Mode, REF- = GND

The denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25C. (Note 3)
CONDITIONS MIN GND - 0.3V GND - 0.3V -FS 0.5VREF/Gain FS/216 0.1 GND 0.1 11 11 11 -10 -10 -100 -100 1 1 1 1 50 120 10 10 100 100 VCC + - 0.1V REF VCC V V V pF pF pF nA nA nA nA ns dB TYP MAX VCC + 0.3V VCC + 0.3V +FS UNITS V V V V
DIGITAL INPUTS AND DIGITAL OUTPUTS
SYMBOL VIH VIL VIH VIL IIN IIN CIN CIN VOH VOL VOH VOL IOZ PARAMETER High Level Input Voltage (CS, FO, SDI) Low Level Input Voltage (CS, FO, SDI) High Level Input Voltage (SCK) Low Level Input Voltage (SCK) Digital Input Current (CS, FO, SDI) Digital Input Current (SCK) Digital Input Capacitance (CS, FO, SDI) Digital Input Capacitance (SCK) High Level Output Voltage (SDO) Low Level Output Voltage (SDO) High Level Output Voltage (SCK) Low Level Output Voltage (SCK) Hi-Z Output Leakage (SDO) CONDITIONS 2.7V VCC 5.5V 2.7V VCC 5.5V
The denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25C. (Note 3)
MIN

TYP
MAX 0.5
UNITS V V V V A A pF pF V
VCC - 0.5 VCC - 0.5 0.5 -10 -10 10 10 10 10
2.7V VCC 5.5V (Notes 10, 15) 2.7V VCC 5.5V (Notes 10, 15) 0V VIN VCC 0V VIN VCC (Notes 10, 15) (Notes 10, 15) IO = -800A IO = 1.6mA IO = -800A (Notes 10, 17) IO = 1.6mA (Notes 10, 17)

VCC - 0.5 0.4 VCC - 0.5 0.4 -10 10
V V V A
POWER REQUIREMENTS
SYMBOL VCC ICC PARAMETER Supply Voltage Supply Current
The denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25C. (Note 3)
CONDITIONS
MIN 2.7

TYP 160 200 1
MAX 5.5 275 300 2
UNITS V A A A
2486f
Conversion Current (Note 12) Temperature Measurement (Note 12) Sleep Mode (Note 12)
4
LTC2486 DIGITAL INPUTS AND DIGITAL OUTPUTS
SYMBOL fEOSC tHEO tLEO tCONV_1 PARAMETER External Oscillator Frequency Range External Oscillator High Period External Oscillator Low Period Conversion Time for 1x Speed Mode 50Hz Mode 60Hz Mode Simultaneous 50/60Hz Mode External Oscillator 50Hz Mode 60Hz Mode Simultaneous 50/60Hz Mode External Oscillator Internal Oscillator (Notes 10, 17) External Oscillator (Notes 10, 11, 15) (Notes 10, 17) (Notes 10, 11, 15) (Notes 10, 11, 15) (Notes 10, 11, 15) Internal Oscillator (Notes 10, 17) External Oscillator (Notes 10, 11, 15) (Notes 10, 11, 15)

The denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25C. (Note 3)
CONDITIONS (Note 16)

MIN 10 0.125 0.125 157.2 131 144.1 78.7 65.6 72.2
TYP
MAX 4000 50 50
UNITS kHz s s ms ms ms ms ms ms ms ms kHz kHz
160.3 133.6 146.9 41036/fEOSC (in kHz) 80.3 66.9 73.6 20556/fEOSC (in kHz) 38.4 fEOSC/8
163.5 136.3 149.9 81.9 68.2 75.1
tCONV_2
Conversion Time for 2x Speed Mode
fISCK DISCK fESCK tLESCK tHESCK tDOUT_ISCK tDOUT_ESCK t1 t2 t3 t4 tKQMAX tKQMIN t5 t7 t8
Internal SCK Frequency Internal SCK Duty Cycle External SCK Frequency Range External SCK Low Period External SCK High Period Internal SCK 24-Bit Data Output Time External SCK 24-Bit Data Output Time CS to SDO Low CS to SDO High Z CS to SCK CS to SCK SCK to SDO Valid SDO Hold After SCK SCK Set-Up Before CS SDI Setup Before SCK SDI Hold After SCK
45 125 125 0.61 0.625 192/fEOSC (in kHz) 24/fESCK (in kHz) 0 0 0 50
55 4000
% kHz ns ns
0.64
ms ms ms ns ns ns ns ns ns ns ns ns
200 200 200 200
Internal SCK Mode External SCK Mode (Note 5) (Note 5) (Note 5)

15 50 100 100
Note 1: Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. Exposure to any Absolute Maximum Rating condition for extended periods may affect device reliability and lifetime. Note 2: All voltage values are with respect to GND. Note 3: Unless otherwise specified: VCC = 2.7V to 5.5V VREFCM = VREF/2, FS = 0.5VREF/Gain VIN = IN+ - IN-, VIN(CM) = (IN+ - IN-)/2, where IN+ and IN- are the selected input channels. Note 4: Use internal conversion clock or external conversion clock source with fEOSC = 307.2kHz unless other wise specified. Note 5: Guaranteed by design, not subject to test. Note 6: Integral nonlinearity is defined as the deviation of a code from a straight line passing through the actual endpoints of the transfer curve. The deviation is measured from the center of the quantization band. Note 7: 50Hz mode (internal oscillator) or fEOSC = 256kHz 2% (external oscillator). Note 8: 60Hz mode (internal oscillator) or fEOSC = 307.2kHz 2% (external oscillator).
Note 9: Simultaneous 50Hz/60Hz mode (internal oscillator) or fEOSC = 280kHz 2% (external oscillator). Note 10: The SCK can be configured in external SCK mode or internal SCK mode. In external SCK mode, the SCK pin is used as a digital input and the driving clock is fESCK. In the internal SCK mode, the SCK pin is used as a digital output and the output clock signal during the data output is fISCK. Note 11: The external oscillator is connected to the FO pin. The external oscillator frequency, fEOSC, is expressed in kHz. Note 12: The converter uses its internal oscillator. Note 13: The output noise includes the contribution of the internal calibration operations. Note 14: Guaranteed by design and test correlation. Note 15: The converter is in external SCK mode of operation such that the SCK pin is used as a digital input. The frequency of the clock signal driving SCK during the data output is fESCK and is expressed in Hz. Note 16: Refer to Applications Information section for performance vs data rate graphs. Note 17: The converter in internal SCK mode of operation such that the SCK pin is used as a digital output.
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LTC2486 TYPICAL PERFORMANCE CHARACTERISTICS
Integral Nonlinearity (VCC = 5V, VREF = 5V)
3 2 INL (ppm OF VREF) 1 0 85C -1 -2 -3 -2.5 -2 -1.5 -1 -0.5 0 0.5 1 1.5 INPUT VOLTAGE (V) VCC = 5V VREF = 5V VIN(CM) = 2.5V FO = GND INL (ppm OF VREF) -45C 25C 3 2 1 -45C, 25C, 85C 0 -1 -2 -3 -1.25
Integral Nonlinearity (VCC = 5V, VREF = 2.5V)
VCC = 5V VREF = 2.5V VIN(CM) = 1.25V FO = GND INL (ppm OF VREF) 3 2 1
Integral Nonlinearity (VCC = 2.7V, VREF = 2.5V)
VCC = 2.7V VREF = 2.5V VIN(CM) = 1.25V FO = GND -45C, 25C, 85C 0 -1 -2 -3 -1.25
2
2.5
-0.75
-0.25 0.25 0.75 INPUT VOLTAGE (V)
1.25
2486 G02
-0.75
-0.25 0.25 0.75 INPUT VOLTAGE (V)
1.25
2486 G03
2486 G01
Total Unadjusted Error (VCC = 5V, VREF = 5V)
12 8 TUE (ppm OF VREF) 4 0 -4 -8 -12 -2.5 -2 -1.5 -1 -0.5 0 0.5 1 1.5 INPUT VOLTAGE (V) -45C 12 VCC = 5V VREF = 5V VIN(CM) = 2.5V FO = GND 8 85C TUE (ppm OF VREF) 25C 4 0 -4 -8
Total Unadjusted Error (VCC = 5V, VREF = 2.5V)
VCC = 5V VREF = 2.5V VIN(CM) = 1.25V FO = GND 12 85C 25C TUE (ppm OF VREF) 4 0 -4 -8 8
Total Unadjusted Error (VCC = 2.7V, VREF = 2.5V)
VCC = 2.7V VREF = 2.5V VIN(CM) = 1.25V FO = GND
25C
85C
-45C
-45C
2
2.5
-12 -1.25
-0.75
-0.25 0.25 0.75 INPUT VOLTAGE (V)
1.25
2486 G05
-12 -1.25
-0.75
-0.25 0.25 0.75 INPUT VOLTAGE (V)
1.25
2486 G06
2486 G04
Noise Histogram (6.8sps)
14 12 NUMBER OF READINGS (%) 10,000 CONSECUTIVE READINGS RMS = 0.60V VCC = 5V AVERAGE = -0.69V VREF = 5V 10 VIN = 0V TA = 25C 8 GAIN = 256 6 4 2 0 -3 -2.4 -1.8 -1.2 -0.6 0 0.6 OUTPUT READING (V) 1.2 1.8 14 12 NUMBER OF READINGS (%)
Noise Histogram (7.5sps)
10,000 CONSECUTIVE READINGS RMS = 0.59V VCC = 2.7V AVERAGE = -0.19V VREF = 2.5V 10 VIN = 0V TA = 25C 8 GAIN = 256 6 4 2 0 -3 -2.4 -1.8 -1.2 -0.6 0 0.6 OUTPUT READING (V) 1.2 1.8 5
Long-Term ADC Readings
VCC = 5V, VREF = 5V, VIN = 0V, VIN(CM) = 2.5V 4 TA = 25C, RMS NOISE = 0.60V, GAIN = 256 3 ADC READING (V) 2 1 0 -1 -2 -3 -4 -5 0 10 30 40 20 TIME (HOURS) 50 60
2486 G09
2486 G07
2486 G08
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LTC2486 TYPICAL PERFORMANCE CHARACTERISTICS
RMS Noise vs Input Differential Voltage
1.0 0.9 RMS NOISE (V) 0.8 0.7 0.6 0.5 0.4 -2.5 -2 -1.5 -1 -0.5 0 0.5 1 1.5 2 INPUT DIFFERENTIAL VOLTAGE (V) VCC = 5V VREF = 5V VIN(CM) = 2.5V TA = 25C RMS NOISE (V) 1.0 0.9 0.8 0.7 0.6 0.5 0.4 -1 0 1 2 3 4 5 6 VIN(CM) (V)
2486 G11
RMS Noise vs VIN(CM)
VCC = 5V VREF = 5V VIN = 0V TA = 25C GAIN = 256 RMS NOISE (V) 1.0 0.9 0.8 0.7 0.6 0.5
RMS Noise vs Temperature (TA)
VCC = 5V VREF = 5V VIN = 0V VIN(CM) = GND GAIN = 256
2.5
0.4 -45 -30 -15
0 15 30 45 60 TEMPERATURE (C)
75
90
2486 G10
2486 G12
RMS Noise vs VCC
1.0 0.9 RMS NOISE (V) 0.8 0.7 0.6 0.5 0.4 2.7 1.0 VREF = 2.5V VIN = 0V VIN(CM) = GND TA = 25C GAIN = 256 0.9 RMS NOISE (V) 0.8 0.7 0.6 0.5 0.4 3.1 3.5 3.9 4.3 VCC (V) 4.7 5.1 5.5
RMS Noise vs VREF
VCC = 5V VIN = 0V VIN(CM) = GND TA = 25C GAIN = 256 0.3 0.2 0.1 0 -0.1 -0.2 -0.3 0 1 2 3 VREF (V) 4 5
2486 G14
Offset Error vs VIN(CM)
VCC = 5V VREF = 5V VIN = 0V TA = 25C
OFFSET ERROR (ppm OF VREF)
-1
0
1
3 2 VIN(CM) (V)
4
5
6
2486 G13
2486 G15
Offset Error vs Temperature
0.3 0.2 0.1 0 0.3 VCC = 5V VREF = 5V VIN = 0V VIN(CM) = GND FO = GND 0.2 0.1 0 -0.1 -0.2
Offset Error vs VCC
REF+ = 2.5V REF- = GND VIN = 0V VIN(CM) = GND TA = 25C 0.3 0.2 0.1 0
Offset Error vs VREF
VCC = 5V REF- = GND VIN = 0V VIN(CM) = GND TA = 25C
OFFSET ERROR (ppm OF VREF)
OFFSET ERROR (ppm OF VREF)
-0.1 -0.2
-0.3 -45 -30 -15
0 15 30 45 60 TEMPERATURE (C)
75
90
-0.3 2.7
3.1
3.5
3.9 4.3 VCC (V)
4.7
5.1
5.5
OFFSET ERROR (ppm OF VREF)
-0.1 -0.2
-0.3 0 1 2 3 VREF (V) 4 5
2486 G18
2486 G16
2486 G17
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LTC2486 TYPICAL PERFORMANCE CHARACTERISTICS
On-Chip Oscillator Frequency vs Temperature
310 310
On-Chip Oscillator Frequency vs VCC
VREF = 2.5V VIN = 0V VIN(CM) = GND FO = GND TA = 25C 0 -20 -40 REJECTION (dB) -60 -80 -100 302 -120 300 75 90 -140
PSRR vs Frequency at VCC
VCC = 4.1V DC VREF = 2.5V IN+ = GND IN- = GND FO = GND TA = 25C
308 FREQUENCY (kHz) FREQUENCY (kHz)
308
306
306
304 VCC = 4.1V VREF = 2.5V VIN = 0V VIN(CM) = GND FO = GND 0 15 30 45 60 TEMPERATURE (C)
304
302
300 -45 -30 -15
2.5
3.0
3.5
4.0 VCC (V)
4.5
5.0
5.5
2486 G20
1
10
10k 100k 1k 100 FREQUENCY AT VCC (Hz)
1M
2486 G19
2486 G21
PSRR vs Frequency at VCC
0 -20 -40 REJECTION (dB) -60 -80 -100 -120 -140 0 20 40 60 80 100 120 140 160 180 200 220 FREQUENCY AT VCC (Hz)
2486 G22
PSRR vs Frequency at VCC
VCC = 4.1V DC 0.7V VREF = 2.5V -20 IN+ = GND IN- = GND -40 FO = GND TA = 25C -60 -80 -100 -120 -140 30600 0 200
Conversion Current vs Temperature
FO = GND CS = GND SCK = NC SDO = NC SDI = GND
CONVERSION CURRENT (A)
REJECTION (dB)
VCC = 4.1V DC 1.4V VREF = 2.5V IN+ = GND IN- = GND FO = GND TA = 25C
180
VCC = 5V
160 VCC = 2.7V
140
120
30650
30750 FREQUENCY AT VCC (Hz)
30700
30800
2486 G23
100 -45 -30 -15
0 15 30 45 60 TEMPERATURE (C)
75
90
2486 G24
Sleep Mode Current vs Temperature
2.0 FO = GND 1.8 CS = VCC SCK = NC 1.6 SDO = NC 1.4 SDI = GND 1.2 1.0 0.8 0.6 0.4 0.2 0 -45 -30 -15 0 15 30 45 60 TEMPERATURE (C) 75 90 VCC = 2.7V VCC = 5V 500 450 SUPPLY CURRENT (A)
Conversion Current vs Output Data Rate
VREF = VCC IN+ = GND IN- = GND 400 SCK = NC SDO = NC 350 SDI = GND CS GND F = EXT OSC 300 O TA = 25C 250 200 150 100 0 10 20 30 40 50 60 70 80 90 100 OUTPUT DATA RATE (READINGS/SEC)
2486 G26
SLEEP MODE CURRENT (A)
VCC = 5V
VCC = 3V
2486 G25
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LTC2486 TYPICAL PERFORMANCE CHARACTERISTICS
Integral Nonlinearity (2x Speed Mode; VCC = 5V, VREF = 5V)
3 2 INL (ppm OF VREF) 1 0 -1 -45C -2 -3 -2.5 -2 -1.5 -1 -0.5 0 0.5 1 1.5 INPUT VOLTAGE (V) -2 -3 -1.25 -2 -3 -1.25 25C, 85C 3 VCC = 5V VREF = 5V VIN(CM) = 2.5V FO = GND INL (ppm OF VREF) 2 1 85C 0 -1 -45C, 25C
Integral Nonlinearity (2x Speed Mode; VCC = 5V, VREF = 2.5V)
VCC = 5V VREF = 2.5V VIN(CM) = 1.25V FO = GND INL (ppm OF VREF) 3 2 1
Integral Nonlinearity (2x Speed Mode; VCC = 2.7V, VREF = 2.5V)
VCC = 2.7V VREF = 2.5V VIN(CM) = 1.25V FO = GND 85C 0 -1 -45C, 25C
2
2.5
-0.75
-0.25 0.25 0.75 INPUT VOLTAGE (V)
1.25
2486 G28
-0.75
-0.25 0.25 0.75 INPUT VOLTAGE (V)
1.25
2486 G29
2486 G27
Noise Histogram (2x Speed Mode)
16 RMS = 0.85V 10,000 CONSECUTIVE AVERAGE = 0.184mV 14 READINGS VCC = 5V 12 VREF = 5V VIN = 0V T = 25C 10 A GAIN = 128 8 6 4 2 0 179 0 181.4 186.2 OUTPUT READING (V) 183.8 188.6
2486 G30
RMS Noise vs VREF (2x Speed Mode)
1.0
NUMBER OF READINGS (%)
0.8 RMS NOISE (V)
0.6
0.4 VCC = 5V VIN = 0V VIN(CM) = GND FO = GND TA = 25C GAIN = 128 0 1 3 2 VREF (V) 4 5
2486 G31
0.2
Offset Error vs VIN(CM) (2x Speed Mode)
200 198 196 OFFSET ERROR (V) 194 192 190 188 186 184 182 180 -1 0 1 3 VIN(CM) (V) 2 4 5 6
2486 G32
Offset Error vs Temperature (2x Speed Mode)
240 230 OFFSET ERROR (V) 220 210 200 190 180 170 160 -45 -30 -15 0 15 30 45 60 TEMPERATURE (C) 75 90 VCC = 5V VREF = 5V VIN = 0V VIN(CM) = GND FO = GND
VCC = 5V VREF = 5V VIN = 0V FO = GND TA = 25C
2486 G33
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LTC2486 TYPICAL PERFORMANCE CHARACTERISTICS
Offset Error vs VCC (2x Speed Mode)
250 VREF = 2.5V VIN = 0V VIN(CM) = GND FO = GND TA = 25C 240 230 OFFSET ERROR (V) 220 210 200 190 180 170 0 2 2.5 3 4 3.5 VCC (V) 4.5 5 5.5
2486 G34
Offset Error vs VREF (2x Speed Mode)
VCC = 5V VIN = 0V VIN(CM) = GND FO = GND TA = 25C 0 -20 -40 REJECTION (dB) -60 -80 -100 -120 -140
PSRR vs Frequency at VCC (2x Speed Mode)
VCC = 4.1V DC REF+ = 2.5V REF- = GND IN+ = GND IN- = GND FO = GND TA = 25C
200 OFFSET ERROR (V)
150
100
50
160
0
1
2
3 VREF (V)
4
5
2486 G35
1
10
10k 100k 1k 100 FREQUENCY AT VCC (Hz)
1M
2486 G36
PSRR vs Frequency at VCC (2x Speed Mode)
0 -20 -40 -60 -80 -100 -120 -140 0 20 40 60 80 100 120 140 160 180 200 220 FREQUENCY AT VCC (Hz)
2486 G37
PSRR vs Frequency at VCC (2x Speed Mode)
VCC = 4.1V DC 0.7V REF+ = 2.5V -20 REF- = GND IN+ = GND -40 IN- = GND FO = GND -60 TA = 25C -80 -100 -120 -140 30600 0
RREJECTION (dB)
REJECTION (dB)
VCC = 4.1V DC 1.4V REF+ = 2.5V REF- = GND IN+ = GND IN- = GND FO = GND TA = 25C
30650
30700 30750 FREQUENCY AT VCC (Hz)
30800
2486 G38
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LTC2486 PIN FUNCTIONS
FO (Pin 1): Frequency Control Pin. Digital input that controls the internal conversion clock rate. When FO is connected to GND, the converter uses its internal oscillator running at 307.2kHz. The conversion clock may also be overridden by driving the FO pin with an external clock in order to change the output rate and the digital filter rejection null. SDI (Pin 2): Serial Data Input. This pin is used to select the gain, line frequency rejection mode, 1x or 2x speed mode, temperature sensor, as well as the input channel. The serial data input is applied under control of the serial clock (SCK) during the data output/input operation. The first conversion following a new input or mode change is valid. SCK (Pin 3): Bidirectional, Digital I/O, Clock Pin. In Internal Serial Clock Operation mode, SCK is generated internally and is seen as an output on the SCK pin. In External Serial Clock Operation mode, the digital I/O clock is externally applied to the SCK pin. The Serial Clock operation mode is determined by the logic level applied to the SCK pin at power up and during the most recent falling edge of CS. CS (Pin 4): Active LOW Chip Select. A LOW on this pin enables the digital input/output and wakes up the ADC. Following each conversion, the ADC automatically enters the Sleep mode and remains in this low power state as long as CS is HIGH. A LOW-to-HIGH transition on CS during the data output aborts the data transfer and starts a new conversion. SDO (Pin 5): Three-State Digital Output. During the data output period, this pin is used as the serial data output. When the chip select pin is HIGH, the SDO pin is in a high impedance state. During the conversion and sleep periods, this pin is used as the conversion status output. When the conversion is in progress this pin is HIGH; once the conversion is complete SDO goes low. The conversion status is monitored by pulling CS LOW. GND (Pin 6): Ground. Connect this pin to a common ground plane through a low impedance connection. COM (Pin 7): The common negative input (IN-) for all single ended multiplexer configurations. The voltage on CH0 to CH3 and COM pins can have any value between GND - 0.3V to VCC + 0.3V. Within these limits, the two selected inputs (IN+ and IN-) provide a bipolar input range VIN = (IN+ - IN-) from -0.5 * VREF/Gain to 0.5 * VREF /Gain. Outside this input range, the converter produces unique over-range and under-range output codes. CH0 to CH3 (Pins 8-11): Analog Inputs. May be programmed for single-ended or differential mode. VCC (Pin 12): Positive Supply Voltage. Bypass to GND with a 10F tantalum capacitor in parallel with a 0.1F ceramic capacitor as close to the part as possible. REF+ (Pin 13), REF- (Pin 14): Differential Reference Input. The voltage on these pins can have any value between GND and VCC as long as the reference positive input, REF+, remains more positive than the negative reference input, REF-, by at least 0.1V. The differential voltage VREF = (REF+ - REF-) sets the full-scale range (-0.5 * VREF/Gain to 0.5 * VREF /Gain) for all input channels. Exposed Pad (Pin 15): Ground. This pin is ground and must be soldered to the PCB ground plane. For prototyping purposes, this pin may remain floating.
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LTC2486 FUNCTIONAL BLOCK DIAGRAM
VCC GND REF + REF - CH0 CH1 CH2 CH3 COM IN+ MUX IN- TEMP SENSOR AUTOCALIBRATION AND CONTROL INTERNAL OSCILLATOR FO (INT/EXT)
-
+
SERIAL INTERFACE DECIMATING FIR ADDRESS
2486 F01
DIFFERENTIAL 3RD ORDER MODULATOR
SDI SCK SDO CS
Figure 1. Functional Block Diagram
TEST CIRCUITS
VCC 1.69k SDO 1.69k CLOAD = 20pF SDO CLOAD = 20pF
Hi-Z TO VOH VOL TO VOH VOH TO Hi-Z
2486 TC01
Hi-Z TO VOL VOH TO VOL VOL TO Hi-Z
2486 TC02
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LTC2486 TIMING DIAGRAMS
Timing Diagram Using Internal SCK (SCK HIGH with CS)
CS t1 SDO Hi-Z t3 SCK t7 SDI SLEEP DATA IN/OUT CONVERSION
2486 TD01
t2 Hi-Z tKQMIN tKQMAX
t8
Timing Diagram Using External SCK (SCK LOW with CS)
CS t1 SDO Hi-Z t5 t4 SCK t7 SDI SLEEP DATA IN/OUT CONVERSION
2486 TD02
t2 Hi-Z tKQMIN tKQMAX
t8
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LTC2486 APPLICATIONS INFORMATION
CONVERTER OPERATION Converter Operation Cycle The LTC2486 is a multi-channel, low power, delta-sigma, analog-to-digital converter with an easy-to-use, 4-wire interface and automatic differential input current cancellation. Its operation is made up of four states (See Figure 2). The converter operating cycle begins with the conversion, followed by the sleep state, and ends with the data input/ output cycle. The 4-wire interface consists of serial data output (SDO), serial clock (SCK), chip select (CS) and serial data input (SDI).The interface, timing, operation cycle, and data output format is compatible with Linear's entire family of SPI converters. Initially, at power up, the LTC2486 performs a conversion. Once the conversion is complete, the device enters the sleep state. While in this sleep state, if CS is HIGH, power consumption is reduced by two orders of magnitude. The part remains in the sleep state as long as CS is HIGH. The conversion result is held indefinitely in a static shift register while the part is in the sleep state. Once CS is pulled LOW, the device powers up, exits the sleep state, and enters the data input/output state. If CS
POWER UP IN+= CH0, IN-= CH1 50/60Hz, GAIN = 1, 1X
is brought HIGH before the first rising edge of SCK, the device returns to the sleep state and the power is reduced. If CS is brought HIGH after the first rising edge of SCK, the data output cycle is aborted and a new conversion cycle begins. The data output corresponds to the conversion just completed. This result is shifted out on the serial data output pin (SDO) under the control of the serial clock pin (SCK). Data is updated on the falling edge of SCK allowing the user to reliably latch data on the rising edge of SCK (See Figure 3). The configuration data for the next conversion is also loaded into the device at this time. Data is loaded from the serial data input pin (SDI) on each rising edge of SCK. The data input/output cycle concludes once 24 bits are read out of the ADC or when CS is brought HIGH. The device automatically initiates a new conversion and the cycle repeats. Through timing control of the CS and SCK pins, the LTC2486 offers several flexible modes of operation (internal or external SCK and free-running conversion modes). These various modes do not require programming and do not disturb the cyclic operation described above. These modes of operation are described in detail in the Serial Interface Timing Modes section. Ease of Use The LTC2486 data output has no latency, filter settling delay, or redundant data associated with the conversion cycle. There is a one-to-one correspondence between the conversion and the output data. Therefore, multiplexing multiple analog inputs is straightforward. Each conversion, immediately following a newly selected input or mode, is valid and accurate to the full specifications of the device. The LTC2486 automatically performs offset and full scale calibration every conversion cycle independent of the input channel selected. This calibration is transparent to the user and has no effect with the operation cycle described above. The advantage of continuous calibration is extreme stability of offset and full-scale readings with respect to time, supply voltage variation, input channel, and temperature drift.
CONVERT
SLEEP
CS = LOW AND SCK
CHANNEL SELECT CONFIGURATION SELECT DATA OUTPUT
2486 F02
Figure 2. LTC2486 State Transition Diagram
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LTC2486 APPLICATIONS INFORMATION
Easy Drive Input Current Cancellation The LTC2486 combines a high precision, delta-sigma ADC with an automatic, differential, input current cancellation front end. A proprietary front end passive sampling network transparently removes the differential input current. This enables external RC networks and high impedance sensors to directly interface to the LTC2486 without external amplifiers. The remaining common mode input current is eliminated by either balancing the differential input impedances or setting the common mode input equal to the common mode reference (see Automatic Differential Input Current Cancellation section). This unique architecture does not require on-chip buffers, thereby enabling signals to swing beyond ground and VCC. Moreover, the cancellation does not interfere with the transparent offset and full-scale auto-calibration and the absolute accuracy (full scale + offset + linearity + drift) is maintained even with external RC networks. Power-Up Sequence The LTC2486 automatically enters an internal reset state when the power supply voltage, VCC, drops below approximately 2V. This feature guarantees the integrity of the conversion result, input channel selection, and serial clock mode. When VCC rises above this threshold, the converter creates an internal power-on-reset (POR) signal with a duration of approximately 4ms. The POR signal clears all internal registers. The conversion immediately following a POR cycle is performed on the input channel IN+ = CH0 and IN- = CH1 with simultaneous 50Hz/60Hz rejection, 1x output rate, and gain = 1. The first conversion following a POR cycle is accurate within the specification of the device if the power supply voltage is restored to (2.7V to 5.5V) before the end of the POR interval. A new input channel, rejection mode, speed mode, temperature selection or gain can be programmed into the device during this first data input/output cycle. Reference Voltage Range This converter accepts a truly differential external reference voltage. The absolute/common mode voltage range for the REF+ and REF- pins covers the entire operating range of the device (GND to VCC). For correct converter operation, VREF must be positive (REF+ > REF-). The LTC2486 differential reference input range is 0.1V to VCC. For the simplest operation, REF+ can be shorted to VCC and REF- can be shorted to GND. The converter output noise is determined by the thermal noise of the front end circuits, and as such, its value in nanovolts is nearly constant with reference voltage. A decrease in reference voltage will not significantly improve the converter's effective resolution. On the other hand, a decreased reference will improve the converter's overall INL performance. Input Voltage Range The analog inputs are truly differential with an absolute, common mode range for the CH0 to CH3 and COM input pins extending from GND - 0.3V to VCC + 0.3V. Outside these limits, the ESD protection devices begin to turn on and the errors due to input leakage current increase rapidly. Within these limits, the LTC2486 converts the bipolar differential input signal VIN = IN+ - IN- (where IN+ and IN- are the selected input channels), from -FS = -0.5 * VREF/Gain to +FS = 0.5 * VREF/Gain where VREF = REF+ - REF-. Outside this range, the converter indicates the overrange or the underrange condition using distinct output codes (see Table 1). Signals applied to the input (CH0 to CH3, COM) may extend 300mV below ground and above VCC. In order to limit any fault current, resistors of up to 5k may be added in series with the input. The effect of series resistance on the converter accuracy can be evaluated from the curves presented in the Input Current/Reference Current sections. In addition, series resistors will introduce a temperature dependent error due to input leakage current. A 1nA input leakage current will develop a 1ppm offset error on a 5k resistor if VREF = 5V. This error has a very strong temperature dependency.
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LTC2486 APPLICATIONS INFORMATION
SERIAL INTERFACE PINS The LTC2486 transmits the conversion result, reads the input configuration, and receives a start of conversion command through a synchronous 3- or 4-wire interface. During the conversion and sleep states, this interface can be used to access the converter status. During the data output state, it is used to read the conversion result, program the input channel, rejection frequency, speed multiplier, select the temperature sensor and set the gain. Serial Clock Input/Output (SCK) The serial clock pin (SCK) is used to synchronize the data input/output transfer. Each bit is shifted out of the SDO pin on the falling edge of SCK and data is shifted into the SDI pin on the rising edge of SCK. The serial clock pin (SCK) can be configured as either a master (SCK is an output generated internally) or a slave (SCK is an input and applied externally). Master mode (Internal SCK) is selected by simply floating the SCK pin. Slave mode (External SCK) is selected by driving SCK low during power up and each falling edge of CS. Specific details of these SCK modes are described in the Serial Interface Timing Modes section. Serial Data Output (SDO) The serial data output pin (SDO) provides the result of the last conversion as a serial bit stream (MSB first) during the data output state. In addition, the SDO pin is used as an end of conversion indicator during the conversion and sleep states. When CS is HIGH, the SDO driver is switched to a high impedance state in order to share the data output line with other devices. If CS is brought LOW during the conversion phase, the EOC bit (SDO pin) will be driven HIGH. Once the conversion is complete, if CS is brought LOW, EOC will be driven LOW indicating the conversion is complete and the result is ready to be shifted out of the device. Chip Select (CS) The active low CS pin is used to test the conversion status, enable I/O data transfer, initiate a new conversion, control the duration of the sleep state, and set the SCK mode. At the conclusion of a conversion cycle, while CS is HIGH, the device remains in a low power sleep state where the supply current is reduced several orders of magnitude. In order to exit the sleep state and enter the data output state, CS must be pulled low. Data is now shifted out the SDO pin under control of the SCK pin as described previously. A new conversion cycle is initiated either at the conclusion of the data output cycle (all 24 data bits read) or by pulling CS HIGH any time between the first and 24th rising edges of the serial clock (SCK). In this case, the data output is aborted and a new conversion begins. Serial Data Input (SDI) The serial data input (SDI) is used to select the input channel, rejection frequency, speed multiplier, gain, and to access the integrated temperature sensor. Data is shifted into the device during the data output/input state on the rising edge of SCK while CS is low. OUTPUT DATA FORMAT The LTC2486 serial output stream is 24 bits long. The first bit indicates the conversion status, the second bit is always zero, and the third bit conveys sign information. The next 17 bits are the conversion result, MSB first. The remaining 4 bits are always LOW. Bit 23 (first output bit) is the end of conversion (EOC) indicator. This bit is available on the SDO pin during the conversion and sleep states whenever CS is LOW. This bit is HIGH during the conversion cycle, goes LOW once the conversion is complete, and is HIGH-Z when CS is HIGH. Bit 22 (second output bit) is a dummy bit (DMY) and is always LOW. Bit 21 (third output bit) is the conversion result sign indicator (SIG). If the selected input (VIN = IN+ - IN-) is greater than or equal to 0V, this bit is HIGH. If VIN < 0, this bit is LOW. Bit 20 (fourth output bit) is the most significant bit (MSB) of the result. This bit in conjunction with Bit 21 also provides underrange and overrange indication. If both Bit 21 and Bit 20 are HIGH, the differential input voltage is above
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LTC2486 APPLICATIONS INFORMATION
+FS. If both Bit 21 and Bit 20 are LOW, the differential input voltage is below -FS. The function of these bits is summarized in Table 1.
Table 1. LTC2486 Status Bits
Input Range VIN 0.5 * VREF/Gain 0V VIN < 0.5 * VREF/Gain -0.5 * VREF/Gain VIN < 0V VIN < -0.5 * VREF/Gain Bit 23 EOC 0 0 0 0 Bit 22 DMY 0 0 0 0 Bit 21 SIG 1 1 0 0 Bit 20 MSB 1 0 1 0
SCK and may be latched on the rising edge of the 24th SCK pulse. On the falling edge of the 24th SCK pulse, SDO goes HIGH indicating the initiation of a new conversion cycle. This bit serves as EOC (Bit 23) for the next conversion cycle. Table 2 summarizes the output data format. As long as the voltage on the IN+ and IN- pins remains between -0.3V and VCC + 0.3V (absolute maximum operating range) a conversion result is generated for any differential input voltage VIN from -FS = -0.5 * VREF/Gain to +FS = 0.5 * VREF /Gain. For differential input voltages greater than +FS, the conversion result is clamped to the value corresponding to +FS + 1LSB. For differential input voltages below -FS, the conversion result is clamped to the value -FS - 1LSB. INPUT DATA FORMAT The LTC2486 serial input word is 16 bits long and contains two distinct sets of data. The first set (SGL, ODD, A2, A1, A0) is used to select the input channel. The second set of data (IM, FA, FB, SPD, GS2, GS1, GS0) is used to select the frequency rejection, speed mode (1x, 2x), temperature measurement, and gain. After power up, the device initiates an internal reset cycle which sets the input channel to CH0-CH1 (IN+ = CH0, IN- = CH1), the frequency rejection to simultaneous 50Hz/60Hz, 1x output rate (auto-calibration enabled), and gain = 1. The first conversion automatically begins at power up using this default configuration. Once the conversion is complete, a new word may be written into the device.
Bits 20 to 4 are the 16-bit plus sign conversion result MSB first. Bit 4 is the least significant bit (LSB16). Bits 3 to 0 are always LOW. Data is shifted out of the SDO pin under control of the serial clock (SCK) (see Figure 3). Whenever CS is HIGH, SDO remains high impedance and SCK is ignored. In order to shift the conversion result out of the device, CS must first be driven LOW. EOC is seen at the SDO pin of the device once CS is pulled LOW. EOC changes in real time as a function of the internal oscillator or the clock applied to the fO pin from HIGH to LOW at the completion of a conversion. This signal may be used as an interrupt for an external microcontroller. Bit 23 (EOC) can be captured on the first rising edge of SCK. Bit 22 is shifted out of the device on the first falling edge of SCK. The final data bit (Bit 0) is shifted out on the on the falling edge of the 23rd
CS
1 SCK (EXTERNAL)
2
3
4
5
6
7
8
9
10
11
12
13
14
15
16
24
SDI
DON'T CARE
1
0
EN
SGL
ODD
A2
A1
A0
EN2
IM
FA
FB
SPD
GS2
GS1
GS0
DON'T CARE
SDO
EOC
"0"
SIG
MSB BIT 9 BIT 0
2486 F03
BIT 23 BIT 22 BIT 21 BIT 20 BIT 19 BIT 18 BIT 17 BIT 16 BIT 15 BIT 14 BIT 13 BIT 12 BIT 11 BIT 10 CONVERSION SLEEP DATA INPUT/OUTPUT
Figure 3. Channel Selection, Configuration Selection and Data Output Timing
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LTC2486 APPLICATIONS INFORMATION
Table 2. LTC2486 Output Data Format
DIFFERENTIAL INPUT VOLTAGE VIN* VIN* FS** FS** - 1LSB 0.5 * FS** 0.5 * FS** - 1LSB 0 -1LSB -0.5 * FS** -0.5 * FS** - 1LSB -FS** VIN* < -FS** BIT 23 EOC 0 0 0 0 0 0 0 0 0 0 BIT 22 DMY 0 0 0 0 0 0 0 0 0 0 BIT 21 SIG 1 1 1 1 1 0 0 0 0 0 BIT 20 MSB 1 0 0 0 0 1 1 1 1 0 BIT 19 0 1 1 0 0 1 1 0 0 1 BIT 18 0 1 0 1 0 1 0 1 0 1 BIT 17 0 1 0 1 0 1 0 1 0 1 ... ... ... ... ... ... ... ... ... ... ... BIT 4 0 1 0 1 0 1 0 1 0 1 BITS 3 TO 0 0000 0000 0000 0000 0000 0000 0000 0000 0000 0000
*The differential input voltage VIN = IN+ - IN-. **The full-scale voltage FS = 0.5 * VREF /Gain.
The first three bits shifted into the device consist of two preamble bits and an enable bit. These bits are used to enable the device configuration and input channel selection. Valid settings for these three bits are 000, 100 and 101. Other combinations should be avoided. If the first three bits are 000 or 100, the following data is ignored (don't care) and the previously selected input channel and configuration remain valid for the next conversion. If the first three bits shifted into the device are 101, then the next five bits select the input channel for the next conversion cycle (see Table 3). The first input bit (SGL) following the 101 sequence determines if the input selection is differential (SGL = 0) or single-ended (SGL = 1). For SGL = 0, two adjacent channels can be selected to form a differential input. For
Table 3 Channel Selection
MUX ADDRESS SGL *0 0 0 0 1 1 1 1 ODD/ SIGN 0 0 1 1 0 0 1 1 A2 0 0 0 0 0 0 0 0 A1 0 0 0 0 0 0 0 0 A0 0 1 0 1 0 1 0 1 IN+ IN+ IN+ IN+ IN- IN+ IN- IN+ IN- IN- IN- IN- 0 IN+ CHANNEL SELECTION 1 IN- IN+ IN- 2 3 COM
SGL = 1, one of four channels is selected as the positive input. The negative input is COM for all single ended operations. The remaining four bits (ODD, A2, A1, A0) determine which channel(s) is/are selected and the polarity (for a differential input). The next serial input bit immediately following the input channel selection is the enable bit for the conversion configuration (EN2). If this bit is set to 0, then the next conversion is performed using the previously selected converter configuration. The second set of configuration data can be loaded into the device by setting EN2 = 1 (see Table 4). The first bit (IM) is used to select the internal temperature sensor. If IM = 1, the following conversion will be performed on the internal temperature sensor rather than the selected input channel. The next two bits (FA and FB) are used to set the rejection frequency. The next bit (SPD) is used to select either the 1x output rate if SPD = 0 (auto-calibration is enabled and the offset is continuously calibrated and removed from the final conversion result) or the 2x output rate if SPD = 1 (offset calibration disabled, multiplexing output rates up to 15Hz with no latency). When IM = 1 (temperature measurement) SPD, GS2, GS1 and GS0 will be ignored and the device will operate in 1x mode. The final 3 bits (GS2, GS1, GS0) are used to set the gain. The configuration remains valid until a new input word with EN = 1 (the first three bits are 101) and EN2 = 1 is shifted into the device.
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LTC2486 APPLICATIONS INFORMATION
Table 4. Converter Configuration
1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 EN SGL ODD A2 A1 A0 EN2 0 X 1 0 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 Any 1 1 Input Channel 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 IM X X 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 1 1 1 1 FA X X FB X X SPD X X 0 0 0 0 0 0 0 0 1 1 1 1 1 1 1 1 Any Speed X X X X X X X X GS2 GS1 GS0 X X X X X X 0 0 0 0 0 1 0 1 0 0 1 1 1 0 0 1 0 1 1 1 0 1 1 1 0 0 0 0 0 1 0 1 0 0 1 1 1 0 0 1 0 1 1 1 0 1 1 1 Any Gain X X X X X X X X CONVERTER CONFIGURATION Keep Previous Keep Previous External Input, Gain = 1, Autocalibration External Input, Gain = 4, Autocalibration External Input, Gain = 8, Autocalibration External Input, Gain = 16, Autocalibration External Input, Gain = 32, Autocalibration External Input, Gain = 64, Autocalibration External Input, Gain = 128, Autocalibration External Input, Gain = 264, Autocalibration External Input, Gain = 1, 2x Speed External Input, Gain = 2, 2x Speed External Input, Gain = 4, 2x Speed External Input, Gain = 8, 2x Speed External Input, Gain = 16, 2x Speed External Input, Gain = 32, 2x Speed External Input, Gain = 64, 2x Speed External Input, Gain = 128, 2x Speed External Input, Simultaneous 50Hz/60Hz Rejection External Input, 50Hz Rejection External Input, 60Hz Rejection Reserved, Do Not Use Temperature Input, Simultaneous 50Hz/60Hz Rejection Temperature Input, 50Hz Rejection Temperature Input, 60Hz Rejection Reserved, Do Not Use
Any Rejection Mode
0 0 1 1 0 0 1 1
0 1 0 1 0 1 0 1
Rejection Mode (FA, FB) The LTC2486 includes a high accuracy on-chip oscillator with no required external components. Coupled with an integrated 4th order digital low pass filter, the LTC2486 rejects line frequency noise. In the default mode, the LTC2486 simultaneously rejects 50Hz and 60Hz by at least 87dB. If more rejection is required, the LTC2486 can be configured to reject 50Hz or 60Hz to better than 110dB. Speed Mode (SPD) Every conversion cycle, two conversions are combined to remove the offset (default mode). This result is free from offset and drift. In applications where the offset is not critical, the auto-calibration feature can be disabled with the benefit of twice the output rate. While operating in the 2x mode (SPD = 1), the linearity and full-scale errors are unchanged from the 1x mode performance. In both the 1x
and 2x mode there is no latency. This enables input steps or multiplexer changes to settle in a single conversion cycle, easing system overhead and increasing the effective conversion rate. During temperature measurements, the 1x mode is always used independent of the value of SPD. GAIN (GS2, GS1, GS0) The input referred gain of the LTC2486 is adjustable from 1 to 256 (see Tables 5a and 5b). With a gain of 1, the differential input range is VREF/2 and the common mode input range is rail-to-rail. As the gain is increased, the differential input range is reduced to 0.5 * VREF/Gain but the common mode input range remains rail-to-rail. As the differential gain is increased, low level voltages are digitized with greater resolution. At a gain of 256, the LTC2486 digitizes an input signal range of 9.76mV (VREF = 5V) with over 16,000 counts.
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LTC2486 APPLICATIONS INFORMATION
Table 5a. Performance vs Gain in Normal Speed Mode (VCC = 5V, VREF = 5V)
GAIN Input Span LSB Noise Free Resolution* Gain Error Offset Error 1 2.5 38.1 65536 5 0.5 4 0.625 9.54 65536 5 0.5 8 0.312 4.77 65536 5 0.5 16 0.156 2.38 65536 5 0.5 32 78m 1.19 65536 5 0.5 64 39m 0.596 65536 5 0.5 128 19.5m 0.298 32768 5 0.5 256 9.76m 0.149 16384 8 0.5 UNIT V V Counts ppm of FS V
Table 5b. Performance vs Gain in 2x Speed Mode (VCC = 5V, VREF = 5V)
GAIN Input Span LSB Noise Free Resolution* Gain Error Offset Error 1 2.5 38.1 65536 5 200 2 1.25 19.1 65536 5 200 4 0.625 9.54 65536 5 200 8 0.312 4.77 65536 5 200 16 0.156 2.38 65536 5 200 32 78m 1.19 65536 5 200 64 39m 0.596 45875 5 200 128 19.5m 0.298 22937 5 200 UNIT V V Counts ppm of FS V
*The resolution in counts is calculated as the FS divided by LSB or the RMS noise value, whichever is larger.
Temperature Sensor The LTC2486 includes an integrated temperature sensor. The temperature sensor is selected by setting IM = 1. The digital output is proportional to the absolute temperature of the device. This feature allows the converter to perform cold junction compensation for external thermocouples or continuously remove the temperature effects of external sensors. The internal temperature sensor output is 28mV at 27C (300K), with a slope of 93.5V/C independent of VREF (see Figures 4 and 5). Slope calibration is not required if the reference voltage (VREF) is known. A 5V reference has a slope of 2.45 LSBs16 /C. The temperature is calculated from the output code (where DATAOUT16 is the decimal representation of the 16-bit result) for a 5V reference using the following formula: TK = DATAOUT16 /2.45 in Kelvin If a different value of VREF is used, the temperature output is: TK = DATAOUT16 /(0.49 * VREF) in Kelvin If the value of VREF is not known, the slope is determined by measuring the temperature sensor at a known temperature TN (in K) and using the following formula: SLOPE = DATAOUT16/TN
This value of slope can be used to calculate further temperature readings using: TK = DATAOUT16 /SLOPE All Kelvin temperature readings can be converted to TC (C) using the fundamental equation: TC = TK - 273 SERIAL INTERFACE TIMING MODES The LTC2486's 4-wire interface is SPI and MICROWIRE compatible. This interface offers several flexible modes of operation. These include internal/external serial clock, 3- or 4-wire I/O, single cycle or continuous conversion. The following sections describe each of these timing modes in detail. In all cases, the converter can use the internal oscillator (FO = LOW) or an external oscillator connected to the FO pin. For each mode, the operating cycle, data input format, data output format, and performance remain the same. Refer to Table 6 for a summary. External Serial Clock, Single Cycle Operation This timing mode uses an external serial clock to shift out the conversion result and CS to monitor and control the state of the conversion cycle (see Figure 6).
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LTC2486 APPLICATIONS INFORMATION
140000 5 4 3 ABSOLUTE ERROR (C) 2 1 0 -1 -2 -3 20000 0 -4 0 100 200 300 TEMPERATURE (K) 400
2486 F04
VCC = 5V VREF = 5V 120000 SLOPE = 314 LSB /K 16 100000 DATAOUT16 80000 60000 40000
-5 -55
-30
-5 20 45 70 TEMPERATURE (C)
95
120
2486 F05
Figure 4. Internal PTAT Digital Output vs Temperature Table 6. Serial Interface Timing Modes
CONFIGURATION External SCK, Single Cycle Conversion External SCK, 3-Wire I/O Internal SCK, Single Cycle Conversion Internal SCK, 3-Wire I/O, Continuous Conversion
Figure 5. Absolute Temperature Error
SCK CONVERSION DATA OUTPUT CONNECTION AND SOURCE CYCLE CONTROL CONTROL WAVEFORMS CS and SCK CS and SCK Figures 6, 7 External External Internal Internal SCK CS Continuous SCK CS Internal Figure 8 Figures 9, 10 Figure 11
2.7V TO 5.5V 12 10F REFERENCE VOLTAGE 0.1V TO VCC 13 14 8 9 ANALOG INPUTS 10 11 7 VCC LTC2486 REF + REF
-
FO
1
= EXTERNAL OSCILLATOR = INTERNAL OSCILLATOR
SDI SCK
2 3 4-WIRE SPI INTERFACE
0.1F
CH0 CH1 CH2 CH3 COM GND 6 CS SDO 5 4
CS 1 SCK (EXTERNAL) 2 3 4 5 6 7 8 9 10 11 12 13 14 15 16 24
SDI
DON'T CARE
1
0
EN
SGL
ODD
A2
A1
A0
EN2
IM
FA
FB
SPD
GS2
GS1
GS0
DON'T CARE
SDO
EOC
"0"
SIG
MSB BIT 12 BIT 11 BIT 10 BIT 9 BIT 0
Hi-Z
BIT 23 BIT 22 BIT 21 BIT 20 BIT 19 BIT 18 BIT 17 BIT 16 BIT 15 BIT 14 BIT 13 CONVERSION SLEEP DATA INPUT/OUTPUT
CONVERSION
2486 F06
Figure 6. External Serial Clock, Single Cycle Operation
2486f
21
LTC2486 APPLICATIONS INFORMATION
The external serial clock mode is selected during the powerup sequence and on each falling edge of CS. In order to enter and remain in the external SCK mode of operation, SCK must be driven LOW both at power up and on each CS falling edge. If SCK is HIGH on the falling edge of CS, the device will switch to the internal SCK mode. The serial data output pin (SDO) is Hi-Z as long as CS is HIGH. At any time during the conversion cycle, CS may be pulled LOW in order to monitor the state of the converter. While CS is LOW, EOC is output to the SDO pin. EOC = 1 while a conversion is in progress and EOC = 0 if the conversion is complete and the device is in the sleep state. Independent of CS, the device automatically enters the sleep state once the conversion is complete; however, in order to reduce the power, CS must be HIGH. When the device is in the sleep state, its conversion result is held in an internal static shift register. The device remains in the sleep state until the first rising edge of SCK is seen while CS is LOW. The input data is then shifted in via the SDI pin on each rising edge of SCK (including the first rising edge). The channel selection and converter configuration mode will be used for the following conversion cycle. If the input channel or converter configuration is changed during this I/O cycle, the new settings take effect on the conversion cycle following the data input/output cycle. The output data is shifted out the SDO pin on each falling edge of SCK. This enables external circuitry to latch the output on the rising edge of SCK. EOC can be latched on the first rising edge of SCK and the last bit of the conversion result can be latched on the 24th rising edge of SCK. On the 24th falling edge of SCK, the device begins a new conversion and SDO goes HIGH (EOC = 1) indicating a conversion is in progress. At the conclusion of the data cycle, CS may remain LOW and EOC monitored as an end-of-conversion interrupt. Typically, CS remains LOW during the data output/input state. However, the data output state may be aborted by pulling CS HIGH any time between the 1st falling edge and the 24th falling edge of SCK (see Figure 7). On the rising edge of CS, the device aborts the data output state and immediately initiates a new conversion. In order to program a new input channel, 8 SCK clock pulses are required. If the data output sequence is aborted prior to the 8th falling edge of SCK, the new input data is ignored and the previously selected input channel remains valid. If the rising edge of CS occurs after the 8th falling edge of SCK, the new input channel is loaded and valid for the next conversion cycle. If CS goes high between the 8th falling edge and the 16th falling edge of SCK, the new channel is still loaded, but the converter configuration remains unchanged. In order to program both the input channel and converter configuration, CS must go high after the 16th falling edge of SCK (at this point all data has been shifted into the device). External Serial Clock, 3-Wire I/O This timing mode uses a 3-wire serial I/O interface. The conversion result is shifted out of the device by an externally generated serial clock (SCK) signal (see Figure 8). CS is permanently tied to ground, simplifying the user interface or isolation barrier. The external serial clock mode is selected at the end of the power-on reset (POR) cycle. The POR cycle typically concludes 4ms after VCC exceeds 2V. The level applied to SCK at this time determines if SCK is internally generated or externally applied. In order to enter the external SCK mode, SCK must be driven LOW prior to the end of the POR cycle. Since CS is tied LOW, the end-of-conversion (EOC) can be continuously monitored at the SDO pin during the convert and sleep states. EOC may be used as an interrupt to an external controller. EOC = 1 while the conversion is in progress and EOC = 0 once the conversion is complete.
2486f
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LTC2486 APPLICATIONS INFORMATION
2.7V TO 5.5V 12 10F REFERENCE VOLTAGE 0.1V TO VCC 13 14 8 9 ANALOG INPUTS 10 11 7 VCC LTC2486 REF + REF - CH0 CH1 CH2 CH3 COM GND 6 CS SDO 5 4 SDI SCK 2 3 4-WIRE SPI INTERFACE FO 1 = EXTERNAL OSCILLATOR = INTERNAL OSCILLATOR
0.1F
CS 1 SCK (EXTERNAL) 2 3 4 5 6 7 8
SDI
DON'T CARE
1
0
EN
SGL
ODD
A2
A1
A0
DON'T CARE
SDO
EOC
"0"
SIG
MSB BIT 15
Hi-Z
2486 F07
BIT 23 BIT 22 BIT 21 BIT 20 BIT 19 BIT 18 BIT 17 BIT 16 CONVERSION SLEEP DATA INPUT/OUTPUT
CONVERSION
SLEEP
Figure 7. External Serial Clock, Reduced Output Data Length and Valid Channel Selection
2.7V TO 5.5V 12 10F REFERENCE VOLTAGE 0.1V TO VCC 13 14 8 9 ANALOG INPUTS 10 11 7 VCC LTC2486 REF + REF
-
FO
1
= EXTERNAL OSCILLATOR = INTERNAL OSCILLATOR
SDI SCK 5
2 3 3-WIRE SPI INTERFACE
0.1F
CH0 CH1 CH2 CH3 COM GND 6 SDO CS 4
CS 1 SCK (EXTERNAL) 2 3 4 5 6 7 8 9 10 11 12 13 14 15 16 24
SDI
DON'T CARE
1
0
EN
SGL
ODD
A2
A1
A0
EN2
IM
FA
FB
SPD
GS2
GS1
GS0
DON'T CARE
SDO
EOC
"0"
SIG
MSB BIT 12 BIT 11 BIT 10 BIT 9 BIT 0
2486 F08
BIT 23 BIT 22 BIT 21 BIT 20 BIT 19 BIT 18 BIT 17 BIT 16 BIT 15 BIT 14 BIT 13 CONVERSION SLEEP DATA INPUT/OUTPUT
CONVERSION
Figure 8. External Serial Clock, 3-Wire Operation (CS = 0)
2486f
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LTC2486 APPLICATIONS INFORMATION
On the falling edge of EOC, the conversion result is loading into an internal static shift register. The output data can now be shifted out the SDO pin under control of the externally applied SCK signal. Data is updated on the falling edge of SCK. The input data is shifted into the device through the SDI pin on the rising edge of SCK. On the 24th falling edge of SCK, SDO goes HIGH, indicating a new conversion has begun. This data now serves as EOC for the next conversion. Internal Serial Clock, Single Cycle Operation This timing mode uses the internal serial clock to shift out the conversion result and CS to monitor and control the state of the conversion cycle (see Figure 9). In order to select the internal serial clock timing mode, the serial clock pin (SCK) must be floating or pulled HIGH before the conclusion of the POR cycle and prior to each falling edge of CS. An internal weak pull-up resistor is active on the SCK pin during the falling edge of CS; therefore, the internal SCK mode is automatically selected if SCK is not externally driven.
2.7V TO 5.5V 12 10F REFERENCE VOLTAGE 0.1V TO VCC 13 14 8 9 ANALOG INPUTS 10 11 7 2486 REF + REF
-
The serial data output pin (SDO) is Hi-Z as long as CS is HIGH. At any time during the conversion cycle, CS may be pulled low in order to monitor the state of the converter. Once CS is pulled LOW, SCK goes LOW and EOC is output to the SDO pin. EOC = 1 while the conversion is in progress and EOC = 0 if the device is in the sleep state. When testing EOC, if the conversion is complete (EOC = 0), the device will exit sleep state. In order to return to the sleep state and reduce the power consumption, CS must be pulled HIGH before the device pulls SCK HIGH. When the device is using its own internal oscillator (FO is tied LOW), the first rising edge of SCK occurs 12s (tEOCTEST = 12s) after the falling edge of CS. If FO is driven by an external oscillator of frequency fEOSC, then tEOCTEST = 3.6/fEOSC. If CS remains LOW longer than tEOCTEST, the first rising edge of SCK will occur and the conversion result is shifted out the SDO pin on the falling edge of SCK. The serial input word (SDI) is shifted into the device on the rising edge of SCK. After the 24th rising edge of SCK a new conversion automatically begins. SDO goes HIGH (EOC = 1) and SCK
1 = EXTERNAL OSCILLATOR = INTERNAL OSCILLATOR VCC 2 3 4-WIRE SPI INTERFACE OPTIONAL 10k
FO
SDI SCK
0.1F
CH0 CH1 CH2 CH3 COM GND 6 CS SDO 5 4
CS 1 SCK (INTERNAL) 2 3 4 5 6 7 8 9 10 11 12 13 14 15 16 24
SDI
DON'T CARE
1
0
EN
SGL
ODD
A2
A1
A0
EN2
IM
FA
FB
SPD
GS2
GS1
GS0
DON'T CARE
SDO
EOC
"0"
SIG
MSB BIT 12 BIT 11 BIT 10 BIT 9 BIT 0
Hi-Z
2486 F09
BIT 23 BIT 22 BIT 21 BIT 20 BIT 19 BIT 18 BIT 17 BIT 16 BIT 15 BIT 14 BIT 13 CONVERSION SLEEP DATA INPUT/OUTPUT
CONVERSION
Figure 9. Internal Serial Clock, Single Cycle Operation
2486f
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LTC2486 APPLICATIONS INFORMATION
remains HIGH for the duration of the conversion cycle. Once the conversion is complete, the cycle repeats. Typically, CS remains LOW during the data output state. However, the data output state may be aborted by pulling CS HIGH any time between the 1st rising edge and the 32nd falling edge of SCK (see Figure 10). On the rising edge of CS, the device aborts the data output state and immediately initiates a new conversion. In order to program a new input channel, 8 SCK clock pulses are required. If the data output sequence is aborted prior to the 8th falling edge of SCK, the new input data is ignored and the previously selected input channel remains valid. If the rising edge of CS occurs after the 8th falling edge of SCK, the new input channel is loaded and valid for the next conversion cycle. If CS goes high between the 8th falling edge and the 16th falling edge of SCK, the new channel is still loaded, but the converter configuration remains unchanged. In order to program both the input channel and converter configuration, CS must go high after the 16th falling edge of SCK (at this point all data has been shifted into the device).
2.7V TO 5.5V 12 10F REFERENCE VOLTAGE 0.1V TO VCC 13 14 8 9 ANALOG INPUTS 10 11 7 2486 REF + REF
-
Internal Serial Clock, 3-Wire I/O, Continuous Conversion. This timing mode uses a 3-wire interface. The conversion result is shifted out of the device by an internally generated serial clock (SCK) signal (see Figure 11). In this case, CS is permanently tied to ground, simplifying the user interface or transmission over an isolation barrier. The internal serial clock mode is selected at the end of the power-on reset (POR) cycle. The POR cycle is concluded approximately 4ms after VCC exceeds 2V. An internal weak pull-up is active during the POR cycle; therefore, the internal serial clock timing mode is automatically selected if SCK is floating or driven HIGH. During the conversion, the SCK and the serial data output pin (SDO) are HIGH (EOC = 1). Once the conversion is complete, SCK and SDO go LOW (EOC = 0) indicating the conversion has finished and the device has entered the sleep state. The device remains in the sleep state a minimum amount of time (1/2 the internal SCK period) then immediately begins outputting and inputting data.
FO
1
= EXTERNAL OSCILLATOR = INTERNAL OSCILLATOR VCC
SDI SCK
2 3 4-WIRE SPI INTERFACE
0.1F
OPTIONAL 10k
CH0 CH1 CH2 CH3 COM GND 6 CS SDO 5 4
CS 1 SCK (INTERNAL) 2 3 4 5 6 7 8 9 10 11 12 13 14 15 16
SDI
DON'T CARE
1
0
EN
SGL
ODD
A2
A1
A0
EN2
IM
FA
FB
SPD
GS2
GS1
GS0
DON'T CARE
SDO
EOC
"0"
SIG
MSB BIT 12 BIT 11 BIT 10 BIT 9 BIT 8 BIT 7
Hi-Z
2486 F10
BIT 23 BIT 22 BIT 21 BIT 20 BIT 19 BIT 18 BIT 17 BIT 16 BIT 15 BIT 14 BIT 13 CONVERSION SLEEP DATA INPUT/OUTPUT
CONVERSION
Figure 10. Internal Serial Clock, Reduced Data Output Length with Valid Channel and Configuration Selection
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LTC2486 APPLICATIONS INFORMATION
2.7V TO 5.5V 12 10F REFERENCE VOLTAGE 0.1V TO VCC 13 14 8 9 ANALOG INPUTS 10 11 7 VCC LTC2486 REF + REF - CH0 CH1 CH2 CH3 COM GND 6 SDO CS 5 4 SDI SCK 2 3 3-WIRE SPI INTERFACE FO 1 = EXTERNAL OSCILLATOR = INTERNAL OSCILLATOR VCC OPTIONAL 10k
0.1F
CS 1 SCK (INTERNAL) 2 3 4 5 6 7 8 9 10 11 12 13 14 15 16 24
SDI
DON'T CARE
1
0
EN
SGL
ODD
A2
A1
A0
EN2
IM
FA
FB
SPD
GS2
GS1
GS0
DON'T CARE
SDO
EOC
"0"
SIG
MSB BIT 12 BIT 11 BIT 10 BIT 9 BIT 0
2486 F11
BIT 23 BIT 22 BIT 21 BIT 20 BIT 19 BIT 18 BIT 17 BIT 16 BIT 15 BIT 14 BIT 13 CONVERSION DATA INPUT/OUTPUT
CONVERSION
Figure 11. Internal Serial Clock, Continuous Operation
The input data is shifted through the SDI pin on the rising edge of SCK (including the first rising edge) and the output data is shifted out the SDO pin on the falling edge of SCK. The data input/output cycle is concluded and a new conversion automatically begins after the 24th rising edge of SCK. During the next conversion, SCK and SDO remain HIGH until the conversion is complete. The Use of a 10k Pull-Up on SCK for Internal SCK Selection If CS is pulled HIGH while the converter is driving SCK LOW, the internal pull-up is not available to restore SCK to a logic HIGH state if SCK is floating. This will cause the device to exit the internal SCK mode on the next falling edge of CS. This can be avoided by adding an external 10k pull-up resistor to the SCK pin. Whenever SCK is LOW, the LTC2486's internal pull-up at SCK is disabled. Normally, SCK is not externally driven if the device is operating in the internal SCK timing mode. However, certain applications may require an external
driver on SCK. If the driver goes Hi-Z after outputting a LOW signal, the internal pull-up is disabled. An external 10k pull-up resistor prevents the device from exiting the internal SCK mode under this condition. A similar situation may occur during the sleep state when CS is pulsed HIGH-LOW-HIGH in order to test the conversion status. If the device is in the sleep state (EOC = 0), SCK will go LOW. If CS goes HIGH before the time tEOCtest, the internal pull-up is activated. If SCK is heavily loaded, the internal pull-up may not restore SCK to a HIGH state before the next falling edge of CS. The external 10k pull-up resistor prevents the device from exiting the internal SCK mode under this condition. PRESERVING THE CONVERTER ACCURACY The LTC2486 is designed to reduce as much as possible sensitivity to device decoupling, PCB layout, anti-aliasing circuits, line frequency perturbations, and temperature sensitivity. In order to achieve maximum performance a few simple precautions should be observed.
2486f
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LTC2486 APPLICATIONS INFORMATION
Digital Signal Levels The LTC2486's digital interface is easy to use. Its digital inputs SDI, FO, CS, and SCK (in external serial clock mode) accept standard CMOS logic levels. Internal hysteresis circuits can tolerate edge transition times as slow as 100s. The digital input signal range is 0.5V to VCC - 0.5V. During transitions, the CMOS input circuits draw dynamic current. For optimal performance, application of signals to the serial data interface should be reserved for the sleep and data output periods. During the conversion period, overshoot and undershoot of fast digital signals applied to both the serial digital interface and the external oscillator pin (FO) may degrade the converter performance. Undershoot and overshoot occur due to impedance mismatch of the circuit board trace at the converter pin when the transition time of an external control signal is less than twice the propagation delay from the driver to the input pin. For reference, on a regular FR-4 board, the propagation delay is approximately 183ps/inch. In order to prevent overshoot, a driver with a 1ns transition time must be connected to the converter through a trace shorter than 2.5 inches. This becomes difficult when shared control lines are used and multiple reflections occur.
INPUT MULTIPLEXER 100 INTERNAL SWITCH NETWORK 10k
Parallel termination near the input pin of the LTC2486 will eliminate this problem, but will increase the driver power dissipation. A series resistor from 27 to 54 (depending on the trace impedance and connection) placed near the driver will also eliminate over/under shoot without additional driver power dissipation. For many applications, the serial interface pins (SCK, SDI, CS, FO) remain static during the conversion cycle and no degradation occurs. On the other hand, if an external oscillator is used (FO driven externally) it is active during the conversion cycle. Moreover, the digital filter rejection is minimal at the clock rate applied to FO. Care must be taken to ensure external inputs and reference lines do not cross this signal or run near it. These issues are avoided when using the internal oscillator. Driving the Input and Reference The input and reference pins of the LTC2486 are connected directly to a switched capacitor network. Depending on the relationship between the differential input voltage and the differential reference voltage, these capacitors are switched between these four pins. Each time a capacitor is switched between two of these pins, a small amount of charge is transferred. A simplified equivalent circuit is shown in Figure 12.
IIN+ IN+ IIN-
I IN+
() (
AVG
= I IN-
()
AVG
=
VIN(CM) - VREF(CM) 0.5 * REQ
I REF + where :
)
1.5VREF + VREF(CM) - VIN(CM) 0.5 * REQ
(
)-
AVG
VIN2 VREF * REQ
100 IN- IREF+ REF+ IREF-
10k
VREF = REF + - REF - REF + - REF - VREF(CM) = 2 CEQ 12pF VIN = IN+ - IN- , WHERE IN+ AND IN- ARE THE SELECTED INPUT CHANNELS IN+ - IN- VIN(CM) = 2 REQ = 2.71M INTERNAL OSCILLATOR 60Hz MODE REQ = 2.98M INTERNAL OSCILLATOR 50Hz/60Hz MODE REQ = 0.833 * 1012 /fEOSC EXTERNAL OSCILLATOR
10k
10k REF- SWITCHING FREQUENCY fSW = 123kHz INTERNAL OSCILLATOR fSW = 0.4 * fEOSC EXTERNAL OSCILLATOR
2486 F12
(
)
Figure 12. LTC2486 Equivalent Analog Input Circuit
2486f
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LTC2486 APPLICATIONS INFORMATION
When using the LTC2486's internal oscillator, the input capacitor array is switched at 123kHz. The effect of the charge transfer depends on the circuitry driving the input/reference pins. If the total external RC time constant is less than 580ns the errors introduced by the sampling process are negligible since complete settling occurs. Typically, the reference inputs are driven from a low impedance source. In this case, complete settling occurs even with large external bypass capacitors. The inputs (CH0 to CH3, COM), on the other hand, are typically driven from larger source resistances. Source resistances up to 10k may interface directly to the LTC2486 and settle completely; however, the addition of external capacitors at the input terminals in order to filter unwanted noise (anti-aliasing) results in incomplete settling. Automatic Differential Input Current Cancellation In applications where the sensor output impedance is low (up to 10k with no external bypass capacitor or up to 500 with 0.001F bypass), complete settling of the input occurs. In this case, no errors are introduced and direct digitization is possible. For many applications, the sensor output impedance combined with external input bypass capacitors produces RC time constants much greater than the 580ns required for 1ppm accuracy. For example, a 10k bridge driving a 0.1F capacitor has a time constant an order of magnitude greater than the required maximum. The LTC2486 uses a proprietary switching algorithm that forces the average differential input current to zero independent of external settling errors. This allows direct digitization of high impedance sensors without the need of buffers. The switching algorithm forces the average input current on the positive input (IIN+) to be equal to the average input current on the negative input (IIN-). Over the complete conversion cycle, the average differential input current (IIN+ - IIN-) is zero. While the differential input current is zero, the common mode input current (IIN+ + IIN-)/2 is proportional to the difference between the common mode input voltage (VIN(CM)) and the common mode reference voltage (VREF(CM)). In applications where the input common mode voltage is equal to the reference common mode voltage, as in the case of a balanced bridge, both the differential and common mode input currents are zero. The accuracy of the converter is not compromised by settling errors. In applications where the input common mode voltage is constant but different from the reference common mode voltage, the differential input current remains zero while the common mode input current is proportional to the difference between VIN(CM) and VREF(CM). For a reference common mode voltage of 2.5V and an input common mode of 1.5V, the common mode input current is approximately 0.74A. This common mode input current does not degrade the accuracy if the source impedances tied to IN+ and IN- are matched. Mismatches in source impedance lead to a fixed offset error but do not effect the linearity or full scale reading. A 1% mismatch in a 1k source resistance leads to a 74V shift in offset voltage. In applications where the common mode input voltage varies as a function of the input signal level (single ended type sensors), the common mode input current varies proportionally with input voltage. For the case of balanced input impedances, the common mode input current effects are rejected by the large CMRR of the LTC2486, leading to little degradation in accuracy. Mismatches in source impedances lead to gain errors proportional to the difference between the common mode input and common mode reference. 1% mismatches in 1k source resistances lead to gain errors on the order of 15ppm. Based on the stability of the internal sampling capacitors and the accuracy of the internal oscillator, a one-time calibration will remove this error. In addition to the input sampling current, the input ESD protection diodes have a temperature dependent leakage current. This current, nominally 1nA (10nA Max), results in a small offset shift. A 1k source resistance will create a 1V typical and a 10V maximum offset voltage. Reference Current Similar to the analog inputs, the LTC2486 samples the differential reference pins (REF+ and REF-) transferring small amounts of charge to and from these pins, thus producing a dynamic reference current. If incomplete settling occurs (as a function the reference source resistance
2486f
28
LTC2486 APPLICATIONS INFORMATION
and reference bypass capacitance) linearity and gain errors are introduced. For relatively small values of external reference capacitance (CREF < 1nF), the voltage on the sampling capacitor settles for reference impedances of many k (if CREF = 100pF up to 10k will not degrade the performance) (see Figures 13 and 14). In cases where large bypass capacitors are required on the reference inputs (CREF > 0.01F) full-scale and linearity errors are proportional to the value of the reference resistance. Every ohm of reference resistance produces a full-scale error of approximately 0.5ppm (while operating in simultaneous 50Hz/60Hz mode) (see Figures 15 and 16). If the input common mode voltage is equal to the reference common mode voltage, a linearity error of approximately
90 80 70 +FS ERROR (ppm) 60 50 40 30 20 10 0 -10 0 10 1k 100 RSOURCE () 10k 100k
2486 F13
0.67ppm per 100 of reference resistance results (see Figure 17). In applications where the input and reference common mode voltages are different, the errors increase.
500 VCC = 5V VREF = 5V VIN+ = 3.75V VIN- = 1.25V FO = GND TA = 25C CREF = 1F, 10F
400 +FS ERROR (ppm)
300
CREF = 0.1F
200 CREF = 0.01F 100
0
0
200
600 400 RSOURCE ()
800
1000
2486 F15
Figure 15. +FS Error vs RSOURCE at VREF (Large CREF)
VCC = 5V VREF = 5V VIN+ = 3.75V VIN- = 1.25V FO = GND TA = 25C CREF = 0.01F CREF = 0.001F CREF = 100pF CREF = 0pF 0
-100 -FS ERROR (ppm) CREF = 0.01F -200 CREF = 1F, 10F -300 VCC = 5V VREF = 5V VIN+ = 1.25V VIN- = 3.75V FO = GND TA = 25C 0 200 600 400 RSOURCE () CREF = 0.1F
-400
-500
800
1000
2486 F16
Figure 13. +FS Error vs RSOURCE at VREF (Small CREF)
10 0 -10 -FS ERROR (ppm) -20 -30 -40 -50 VCC = 5V -60 VREF = 5V V + = 1.25V -70 VIN- = 3.75V IN -80 FO = GND TA = 25C -90 10 0 CREF = 0.01F CREF = 0.001F CREF = 100pF CREF = 0pF
Figure 16. -FS Error vs RSOURCE at VREF (Large CREF)
10 VCC = 5V 8 VREF = 5V VIN(CM) = 2.5V 6 T = 25C A 4 CREF = 10F 2 0 -2 -4 -6 -8 R = 100
R = 1k
INL (ppm OF VREF)
R = 500
1k 100 RSOURCE ()
10k
100k
2486 F14
-10 - 0.5
- 0.3
0.1 - 0.1 VIN/VREF
0.3
0.5
2486 F17
Figure 14. -FS Error vs RSOURCE at VREF (Small CREF)
Figure 17. INL vs Differential Input Voltage and Reference Source Resistance for CREF > 1F
2486f
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LTC2486 APPLICATIONS INFORMATION
A 1V difference in between common mode input and common mode reference results in a 6.7ppm INL error for every 100 of reference resistance. In addition to the reference sampling charge, the reference ESD protection diodes have a temperature dependent leakage current. This leakage current, nominally 1nA (10nA max) results in a small gain error. A 100 reference resistance will create a 0.5V full scale error. Normal Mode Rejection and Anti-aliasing One of the advantages delta-sigma ADCs offer over conventional ADCs is on-chip digital filtering. Combined with a large oversample ratio, the LTC2486 significantly simplifies anti-aliasing filter requirements. Additionally, the input current cancellation feature allows external low
0 INPUT NORMAL MODE REJECTION (dB) -10 -20 -30 -50 -60 -70 -80 -90 -100 -110 -120 0 fS 2fS 3fS 4fS 5fS 6fS 7fS 8fS 9fS 10fS11fS12fS DIFFERENTIAL INPUT SIGNAL FREQUENCY (Hz)
2486 F18
pass filtering without degrading the DC performance of the device. The SINC4 digital filter provides excellent normal mode rejection at all frequencies except DC and integer multiples of the modulator sampling frequency (fS) (see Figures 18 and 19). The modulator sampling frequency is fS = 15,360Hz while operating with its internal oscillator and fS = FEOSC/20 when operating with an external oscillator of frequency FEOSC. When using the internal oscillator, the LTC2486 is designed to reject line frequencies. As shown in Figure 20, rejection nulls occur at multiples of frequency fN, where fN is determined by the input control bits FA and FB (fN = 50Hz or 60Hz or 55Hz for simultaneous rejection). Multiples of the modulator sampling rate (fS = fN * 256) only reject noise to 15dB (see Figure 21); if noise sources are present at these frequencies anti-aliasing will reduce their effects.
0 INPUT NORMAL MODE REJECTION (dB) -10 -20 -30 -40 -50 -60 -70 -80 -90 -100 -110 -120 0 fN 2fN 3fN 4fN 5fN 6fN 7fN 8fN INPUT SIGNAL FREQUENCY (Hz) 2486 F20 fN = fEOSC/5120
-40
Figure 18. Input Normal Mode Rejection, Internal Oscillator and 50Hz Rejection Mode
0 INPUT NORMAL MODE REJECTION (dB) -10 -20 -30 -40 -50 -60 -70 -80 -90 -100 -110 -120 0 fS 2fS 3fS 4fS 5fS 6fS 7fS 8fS 9fS 10fS DIFFERENTIAL INPUT SIGNAL FREQUENCY (Hz)
2486 F19
Figure 20. Input Normal Mode Rejection at DC
0 INPUT NORMAL MODE REJECTION (dB) -10 -20 -30 -40 -50 -60 -70 -80 -90 -100 -110 -120 250fN 252fN 254fN 256fN 258fN 260fN 262fN INPUT SIGNAL FREQUENCY (Hz) 2486 F21
Figure 19. Input Normal Mode Rejection, Internal Oscillator and 60Hz Rejection Mode
Figure 21. Input Normal Mode Rejection at fS = 256 * fN
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LTC2486 APPLICATIONS INFORMATION
The user can expect to achieve this level of performance using the internal oscillator, as shown in Figures 22, 23, and 24. Measured values of normal mode rejection are
0 NORMAL MODE REJECTION (dB) -20 -40 - 60 -80 -100 -120 MEASURED DATA CALCULATED DATA VCC = 5V VREF = 5V VIN(CM) = 2.5V VIN(P-P) = 5V TA = 25C
shown superimposed over the theoretical values in all three rejection modes. Traditional high order delta-sigma modulators suffer from potential instabilities at large input signal levels. The proprietary architecture used for the LTC2486 third order modulator resolves this problem and guarantees stability with input signals 150% of full-scale. In many industrial applications, it is not uncommon to have microvolt level signals superimposed over unwanted error sources with several volts of peak-to-peak noise. Figures 25 and 26 show measurement results for the rejection of a 7.5V peak-to-peak noise source (150% of full scale) applied to the LTC2486. From these curves, it is shown that the rejection performance is maintained even in extremely noisy environments.
0 NORMAL MODE REJECTION (dB) -20 -40 - 60 -80 -100 -120 VIN(P-P) = 5V VIN(P-P) = 7.5V (150% OF FULL SCALE)
0
15
30
45
60
75
90 105 120 135 150 165 180 195 210 225 240 INPUT FREQUENCY (Hz)
2486 F22
Figure 22. Input Normal Mode Rejection vs Input Frequency with Input Perturbation of 100% (60Hz Notch)
0 NORMAL MODE REJECTION (dB) -20 -40 - 60 -80 -100 -120 MEASURED DATA CALCULATED DATA
VCC = 5V VREF = 5V VIN(CM) = 2.5V VIN(P-P) = 5V TA = 25C
VCC = 5V VREF = 5V VIN(CM) = 2.5V TA = 25C
0
12.5 25 37.5 50 62.5 75 87.5 100 112.5 125 137.5 150 162.5 175 187.5 200 INPUT FREQUENCY (Hz)
2486 F23
0
15
30
45
60
75
90 105 120 135 150 165 180 195 210 225 240 INPUT FREQUENCY (Hz)
2486 F25
Figure 23. Input Normal Mode Rejection vs Input Frequency with Input Perturbation of 100% (50Hz Notch)
0 NORMAL MODE REJECTION (dB) -20 -40 - 60 -80 -100 -120 MEASURED DATA CALCULATED DATA
Figure 25. Measure Input Normal Mode Rejection vs Input Frequency with Input Perturbation of 150% (60Hz Notch)
0 NORMAL MODE REJECTION (dB) -20 -40 - 60 -80 -100 -120 VIN(P-P) = 5V VIN(P-P) = 7.5V (150% OF FULL SCALE)
VCC = 5V VREF = 5V VIN(CM) = 2.5V VIN(P-P) = 5V TA = 25C
VCC = 5V VREF = 5V VIN(CM) = 2.5V TA = 25C
0
20
40
60
80 100 120 140 INPUT FREQUENCY (Hz)
160
180
200
220
2486 F24
0
12.5 25 37.5 50 62.5 75 87.5 100 112.5 125 137.5 150 162.5 175 187.5 200 INPUT FREQUENCY (Hz)
2486 F26
Figure 24. Input Normal Mode Rejection vs Input Frequency with Input Perturbation of 100% (50Hz/60Hz Notch)
Figure 26. Measure Input Normal Mode Rejection vs Input Frequency with input Perturbation of 150% (50Hz Notch)
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31
LTC2486 APPLICATIONS INFORMATION
Using the 2x speed mode of the LTC2486 alters the rejection characteristics around DC and multiples of fS. The device bypasses the offset calibration in order to increase the output rate. The resulting rejection plots are shown in Figures 27 and 28. 1x type frequency rejection can be achieved using the 2x mode by performing a running average of the conversion results (see Figure 29). Output Data Rate When using its internal oscillator, the LTC2486 produces up to 15 samples per second (sps) with a notch frequency of 60Hz. The actual output data rate depends upon the length of the sleep and data output cycles which are controlled by the user and can be made insignificantly short. When operating with an external conversion clock (FO connected to an external oscillator), the LTC2486 output data rate can be increased. The duration of the conversion cycle is 41036/fEOSC. If fEOSC = 307.2kHz, the converter behaves as if the internal oscillator is used. An increase in fEOSC over the nominal 307.2kHz will translate into a proportional increase in the maximum output data rate (up to a maximum of 100sps). The increase in output
0 INPUT NORMAL REJECTION (dB) 0 fN 2fN 3fN 4fN 5fN 6fN 7fN INPUT SIGNAL FREQUENCY (fN) 8fN INPUT NORMAL REJECTION (dB) -20 -40 -60 -80
rate leads to degradation in offset, full-scale error, and effective resolution as well as a shift in frequency rejection. When using the integrated temperature sensor, the internal oscillator should be used or an external oscillator, fEOSC = 307.2kHz maximum. A change in fEOSC results in a proportional change in the internal notch position. This leads to reduced differential mode rejection of line frequencies. The common mode rejection of line frequencies remains unchanged, thus fully differential input signals with a high degree of symmetry on both the IN+ and IN- pins will continue to reject line frequency noise. An increase in fEOSC also increases the effective dynamic input and reference current. External RC networks will continue to have zero differential input current, but the time required for complete settling (580ns for fEOSC = 307.2kHz) is reduced, proportionally. Once the external oscillator frequency is increased above 1MHz (a more than 3x increase in output rate) the effectiveness of internal auto calibration circuits begins to degrade. This results in larger offset errors, full scale errors, and decreased resolution (see Figures 30 to 37).
0 -20 -40 -60 -80 -100 -120 248 250 252 254 256 258 260 262 264 INPUT SIGNAL FREQUENCY (fN)
2486 F28
-100 -120
2486 F27
Figure 27. Input Normal Mode Rejection 2x Speed Mode
Figure 28. Input Normal Mode Rejection 2x Speed Mode
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32
LTC2486 APPLICATIONS INFORMATION
-70 NORMAL MODE REJECTION (dB) -80 NO AVERAGE -90 -100 -110 -120 -130 -140 60 62 54 56 58 48 50 52 DIFFERENTIAL INPUT SIGNAL FREQUENCY (Hz)
2486 F29
50 40 30
OFFSET ERROR (ppm OF VREF)
+FS ERROR (ppm OF VREF)
VIN(CM) = VREF(CM) VCC = VREF = 5V VIN = 0V FO = EXT CLOCK TA = 85C
3500 3000 2500
VIN(CM) = VREF(CM) VCC = VREF = 5V FO = EXT CLOCK
TA = 85C 2000 1500 1000 500 0 TA = 25C
WITH RUNNING AVERAGE
20 10 0 TA = 25C -10 0 10 20 30 40 50 60 70 80 90 100 OUTPUT DATA RATE (READINGS/SEC)
2486 F30
0 10 20 30 40 50 60 70 80 90 100 OUTPUT DATA RATE (READINGS/SEC)
2486 F31
Figure 29. Input Normal Mode Rejection 2x Speed Mode with and Without Running Averaging
0 -500 -FS ERROR (ppm OF VREF) RESOLUTION (BITS) -1000 TA = 25C TA = 85C -2000
Figure 30. Offset Error vs Output Data Rate and Temperature
18 TA = 25C, 85C RESOLUTION (BITS) 16 16 18
Figure 31. +FS Error vs Output Data Rate and Temperature
TA = 25C TA = 85C
-1500
14
14
-2500 -3000 VIN(CM) = VREF(CM) VCC = VREF = 5V FO = EXT CLOCK 0 10 20 30 40 50 60 70 80 90 100 OUTPUT DATA RATE (READINGS/SEC)
2486 F32
12
VIN(CM) = VREF(CM) VCC = VREF = 5V VIN = 0V FO = EXT CLOCK RES = LOG 2 (VREF/NOISERMS) 0 10 20 30 40 50 60 70 80 90 100 OUTPUT DATA RATE (READINGS/SEC)
2486 F33
-3500
10
12 VIN(CM) = VREF(CM) VCC = VREF = 5V FO = EXT CLOCK RES = LOG 2 (VREF/INLMAX) 10 0 10 20 30 40 50 60 70 80 90 100 OUTPUT DATA RATE (READINGS/SEC)
2486 F34
Figure 32.-FS Error vs Output Data Rate and Temperature
20 VIN(CM) = VREF(CM) VIN = 0V 15 FO = EXT CLOCK TA = 25C RESOLUTION (BITS) 10 VCC = VREF = 5V 5 0 -5 VCC = 5V, VREF = 2.5V -10 0 10 20 30 40 50 60 70 80 90 100 OUTPUT DATA RATE (READINGS/SEC)
2486 F35
Figure 33. Resolution (NoiseRMS 1LSB) vs Output Data Rate and Temperature
18
Figure 34. Resolution (INLMAX 1LSB) vs Output Data Rate and Temperature
18
OFFSET ERROR (ppm OF VREF)
VCC = 5V, VREF = 2.5V, 5V 14
RESOLUTION (BITS)
16
16 VCC = 5V, VREF = 2.5V 14
VCC = VREF = 5V
VIN(CM) = VREF(CM) 12 VIN = 0V FO = EXT CLOCK TA = 25C RES = LOG 2 (VREF/NOISERMS) 10 0 10 20 30 40 50 60 70 80 90 100 OUTPUT DATA RATE (READINGS/SEC)
2486 F36
VIN(CM) = VREF(CM) VIN = 0V 12 REF- = GND FO = EXT CLOCK TA = 25C RES = LOG 2 (VREF/INLMAX) 10 0 10 20 30 40 50 60 70 80 90 100 OUTPUT DATA RATE (READINGS/SEC)
2486 F37
Figure 35. Offset Error vs Output Data Rate and Reference Voltage
Figure 36. Resolution (NoiseRMS 1LSB) vs Output Data Rate and Reference Voltage
Figure 37. Resolution (INLMAX 1LSB) vs Output Data Rate and Reference Voltage
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33
LTC2486 APPLICATIONS INFORMATION
Easy Drive ADCs Simplify Measurement of High Impedance Sensors Delta-Sigma ADCs, with their high accuracy and high noise immunity, are ideal for directly measuring many types of sensors. Nevertheless, input sampling currents can overwhelm high source impedances or low-bandwidth, micropower signal conditioning circuits. The LTC2486 solves this problem by balancing the input currents, thus simplifying or eliminating the need for signal conditioning circuits. A common application for a delta-sigma ADC is thermistor measurement. Figure 38 shows two examples of thermistor digitization benefiting from the Easy Drive technology. The first circuit (applied to input channels CH0 and CH1) uses balanced reference resistors in order to balance the common mode input/reference voltage and balance the differential input source resistance. If reference resistors R1 and R4 are exactly equal, the input current is zero and no errors result. If these resistors have a 1% tolerance, the maximum error in measured resistance is 1.6 due to a shift in common mode voltage; far less than the 1% error of the reference resistors themselves. No amplifier is required, making this an ideal solution in micropower applications. Easy Drive also enables very low power, low bandwidth amplifiers to drive the input to the LTC2486. As shown in Figure 38, CH2 is driven by the LT1494. The LT1494 has excellent DC specs for an amplifier with 1.5A supply current (the maximum offset voltage is 150V and the open loop gain is 100,000). Its 2kHz bandwidth makes it unsuitable for driving conventional delta sigma ADCs. Adding a 1k, 0.1F filter solves this problem by providing a charge reservoir that supplies the LTC2486 instantaneous current, while the 1k resistor isolates the capacitive load from the LT1494. Conventional delta sigma ADCs input sampling current lead to DC errors as a result of incomplete settling in the external RC network. The Easy Drive technology cancels the differential input current. By balancing the negative input (CH3) with a 1k, 0.1F network errors due to the common mode input current are cancelled.
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34
LTC2486 PACKAGE DESCRIPTION
DE Package 14-Lead Plastic DFN (4mm x 3mm)
(Reference LTC DWG # 05-08-1708 Rev A)
0.70 0.05 3.60 0.05
1.70 0.05 2.20 0.05 (2 SIDES) PACKAGE OUTLINE 0.25 0.05 0.50 BSC 3.30 0.05 (2 SIDES) RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS 4.00 0.10 (2 SIDES) R = 0.05 TYP R = 0.115 TYP 8 14 0.40 0.10
3.00 0.10 (2 SIDES) PIN 1 TOP MARK (SEE NOTE 6)
1.70 0.05 (2 SIDES)
PIN 1 NOTCH R = 0.20 OR 0.35 x 45 CHAMFER
(DE14) DFN 0905 REV A
7 0.200 REF 0.75 0.05 3.30 0.05 (2 SIDES)
1 0.25 0.05 0.50 BSC
0.00 - 0.05
BOTTOM VIEW--EXPOSED PAD NOTE: 1. DRAWING PROPOSED TO BE MADE VARIATION OF VERSION (WGED-3) IN JEDEC PACKAGE OUTLINE MO-229 2. DRAWING NOT TO SCALE 3. ALL DIMENSIONS ARE IN MILLIMETERS 4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.15mm ON ANY SIDE 5. EXPOSED PAD SHALL BE SOLDER PLATED 6. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION ON THE TOP AND BOTTOM OF PACKAGE
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Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights.
35
LTC2486 TYPICAL APPLICATION
5V R1 51.1k C4 0.1F IIN+ = 0 R3 10k TO 100k 10F 13 0.1F C3 0.1F 5V 102k 5V R4 51.1k IIN- = 0 14 8 9 10 11 1k LT1494 0.1F 1k 0.1F 7 5V 12 VCC LTC2486 REF + REF- CH0 CH1 CH2 CH3 COM GND
2486 F38
FO
1
= EXTERNAL OSCILLATOR = INTERNAL OSCILLATOR
SDI SCK 5
2 3 3-WIRE SPI INTERFACE
SDO CS
4
+
0.1F 10k TO 100k
6
-
Figure 38. Easy Drive ADCs Simplify Measurement of High Impedance Sensors
RELATED PARTS
PART NUMBER LT1236A-5 LT1460 LT1790 LTC2400 LTC2410 LTC2413 LTC2440 LTC2442 LTC2449 LTC2480 LTC2481 LTC2482 LTC2483 LTC2484 LTC2485 LTC2488 LTC2492 LTC2494 LTC2496/ LTC2498 DESCRIPTION Precision Bandgap Reference, 5V Micropower Series Reference Micropower SOT-23 Low Dropout Reference Family 24-Bit, No Latency ADC in SO-8 24-Bit, No Latency ADC with Differential Inputs 24-Bit, No Latency ADC with Differential Inputs High Speed, Low Noise 24-Bit ADC 24-Bit, High Speed 2-Channel and 4-Channel ADC with Integrated Amplifier 24-Bit, High Speed 8-Channel and 16-Channel ADC 16-Bit ADC with Easy Drive Inputs, 600nV Noise, Programmable Gain, and Temperature Sensor 16-Bit ADC with Easy Drive Inputs, 600nV Noise, I2C Interface, Programmable Gain, and Temperature Sensor 16-Bit ADC with Easy Drive Inputs 16-Bit ADC with Easy Drive Inputs, and I2C Interface 24-Bit ADC with Easy Drive Inputs 24-Bit ADC with Easy Drive Inputs, I2C Interface, and Temperature Sensor 2-Channel/4-Channel 16-Bit ADC with Easy Drive Inputs 2-Channel/4-Channel 24-Bit ADC with Easy Drive Inputs 8-Channel/16-Channel 16-Bit ADC with PGA and Easy Drive Inputs 16-Channel/8-Channel 16-Bit/24-Bit ADC with Easy Drive Inputs, and SPI Interface COMMENTS 0.05% Max Initial Accuracy, 5ppm/C Drift 0.075% Max Initial Accuracy, 10ppm/C Max Drift 0.05% Max Initial Accuracy, 10ppm/C Max Drift 0.3ppm Noise, 4ppm INL, 10ppm Total Unadjusted Error, 200A 0.8VRMS Noise, 2ppm INL Simultaneous 50Hz/60Hz Rejection, 800nVRMS Noise 3.5kHz Output Rate, 200nV Noise, 24.6 ENOBs 8kHz Output Rate, 220nV Noise, Simultaneous 50Hz/60Hz Rejection 8kHz Output Rate, 200nV Noise, Simultaneous 50Hz/60Hz Rejection Pin Compatible with LTC2482/LTC2484 Pin Compatible with LTC2483/LTC2485 Pin Compatible with LTC2480/LTC2484 Pin Compatible with LTC2481/LTC2485 Pin Compatible with LTC2480/LTC2482 Pin Compatible with LTC2481/LTC2483 Pin Compatible with LTC2486/LTC2492 Pin Compatible with LTC2486/LTC2488 Pin Compatible with LTC2498/LTC2496 Timing Compatible with LTC2486
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36 Linear Technology Corporation
(408) 432-1900 FAX: (408) 434-0507
LT 0107 * PRINTED IN USA
1630 McCarthy Blvd., Milpitas, CA 95035-7417
www.linear.com
(c) LINEAR TECHNOLOGY CORPORATION 2007

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